Mapping Wireless Communication Algorithms onto a Reconfigurable
Introduction to Algorithms for Wireless Communication · Introduction to Algorithms for Wireless...
Transcript of Introduction to Algorithms for Wireless Communication · Introduction to Algorithms for Wireless...
![Page 1: Introduction to Algorithms for Wireless Communication · Introduction to Algorithms for Wireless Communication LU Hardware Software Codesign WS15/16 Robert Najvirt TU Wien, Embedded](https://reader033.fdocuments.net/reader033/viewer/2022052015/602c704c362c71020a6dc4c2/html5/thumbnails/1.jpg)
Introduction to Algorithmsfor Wireless Communication
LU Hardware Software CodesignWS15/16
Robert NajvirtTU Wien, Embedded Computing Systems Group
Wien, 16. 10. 2015
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The overall goal
Build an FM receiver:– Tune to carrier frequency
– Demodulate
Show RDS info– Tune to subcarrier
– Demodulate
– Decode
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System overview
Source MixerFilter
Decim.Demod
Mixer FilterInterp.Decim.
Symboldet.
Audio
RDS
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Signal at the input
● IQ samples of baseband signal downmixed from 100.5 MHz
● Sampling rate: 2.5 Msps● How wide is the spectrum?
2.5 MHz! (-1.25 MHz to 1.25 MHz)
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IQ samples?
● Basically samples as complex numbers● In-phase (real) and quadrature (imaginary)
components● An RF signal: A(t)*cos(2πft + ϕ(t))
– We need two dimensions for amplitude and phase
● Main advantage:– sin(x)*sin(y)=0.5[cos(x-y)-cos(x+y)]
– But: ex*ey = ex+y
● Remember: eiϕ is the unit vector with angle ϕ
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IQ sampling
● Generate carrier frequency (100.5 MHz) and a copy of it phase-shifted by π/2
● Multiply the RF signal by the two, then low-pass-filter and sample separately
● Result is the RF signal frequency-shiftedand low-pass-filtered:100.5 MHz ± 1.25 MHzcentered around 0 Hz
[http://www.rfwireless-world.com/Terminology/heterodyne-receiver-versus-homodyne-receiver.html]
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Our input signal
Source MixerFilter
Decim.Demod
Mixer FilterInterp.Decim.
Symboldet.
Audio
RDS
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Our input signal
(real part of the signal)
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Our input signal
(FFT)
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First step
● Tune to the frequency we want:99.9 MHz (OE 3)
● Multiplication with the negative carrier frequency:
A(t)ei2πfct+iθ(t) * ei2π(-fc)t = A(t)eiθ(t)
● The component name: Mixer
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Mixer
Source MixerFilter
Decim.Demod
Mixer FilterInterp.Decim.
Symboldet.
Audio
RDS
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Mixer
Source:
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Mixer
Multiplicand (-carrier): (0.6 MHz = -(99.9-100.5) )
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Mixer
Result:
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Mixer
FFT before:
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Mixer
FFT after:
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Baseband filter
● Select only relevant signal● FM bandwidth is max. 200 kHz
– Low pass filter below 100 kHz
● FIR filter– Length is design parameter, affects SNR
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Decimation
● After filtering, sampling rate unnecessarily high– 100 kHz max. frequency, 2.5 Msps
● We can drop every Nth sample without loss of signal information– N is a design parameter, affects algorithmic
complexity (demodulation, filters) and computation speed later
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Filtering and decimation
Source MixerFilter
Decim.Demod
Mixer FilterInterp.Decim.
Symboldet.
Audio
RDS
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Filtering and decimation
Before:
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Filtering and decimation
After:
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Filtering and decimation
FFT before:
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Filtering and decimation
FFT after:
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FM Modulation
● The amplitude of the carrier is left unchangedbut the frequency is altered:
rf(t) = A(t)ei2πfct+im(t)t
– A(t) constant, frequency deviation m(t) = message
["Amfm3-en-de" by Berserkerus - Own work. Licensed under CC BY-SA 2.5 via Commons - https://commons.wikimedia.org/wiki/File:Amfm3-en-de.gif#/media/File:Amfm3-en-de.gif]
[http://web.stanford.edu/class/ee179/labs/Lab5.html]
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FM modulation
● We already removed the carrier:
ei2πfct+im(t)t * e-i2πfct = eim(t)t
● Frequency deviation = message
● Frequency is phase difference
– With complex signals phase = angle
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FM demodulation #1
● Detect angle difference
● One approximation (has a problem):
angle(sig(t)) – angle(sig(t-1/fs))● Simpler:
angle(sig(t)*conj(sig(t-1/fs)))
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FM demodulation #2
● Differentiate signal and multiply by conjugateof original
(d/dt eim(t)t) * conj(eim(t)t) = im(t) * eim(t)t * e-im(t)t =im(t)
● Differentiation by first order approximation (sig(t)-sig(t-1/fs)) or better with FIR filter
– See recommended reading http://web.stanford.edu/class/ee179/labs/Lab5.html
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Filtering and decimation
Source MixerFilter
Decim.Demod
Mixer FilterInterp.Decim.
Symboldet.
Audio
RDS
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FM demodulation
Before:
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FM demodulation
After (real signal):
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FM demodulation
FFT before:
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FFT after:
FM demodulation
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FM demodulated signal
● Audio output: Low pass below 19 (15) kHz,(resample and) ouput
● RDS: (Again) modulated at 57 ± 2.4 kHz
[Wikipedia]
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Carrier frequency error
● When mixing the (estimated) carrier, an error term remains:
ei2πfct+iθ(t)t * ei2π(-fc+err)t = e-iθ(t)t * ei2πerrt
– A remaining frequency component
● After FM demodulation, this term adds to the message signal
● Assuming it is almost constant, we can correct fc using the low-passed message signal
● Error comes mainly from sampling, not from broadcasting
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Carrier frequency error
● FM audio starts at 30 Hz – use a low pass filter (well) below that; an IIR filter may be used
fc vs. time
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2nd Part
Source MixerFilter
Decim.Demod
Mixer FilterInterp.Decim.
Symboldet.
Audio
RDS
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RDS subband
● Subcarrier is 57 kHz → start with mixer– We know how to do that already
● Next step is low pass (matched) filtering– RDS standard specifies the filter parameters
● The idea behind matched filtering– low-pass@TX and low-pass@RX together give
a filter beneficial for signal quality
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Filtering and decimation
Source MixerFilter
Decim.Demod
Mixer FilterInterp.Decim.
Symboldet.
Audio
RDS
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FFT input:
RDS mixing and filtering
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FFT after mixing and filtering:
RDS mixing and filtering
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RDS mixing and filtering
Signal at input:
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RDS mixing and filtering
Signal after mixing:
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RDS mixing and filtering
Signal after mixing (zoom out):
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RDS mixing and filtering
Signal after mixing and filtering (real part):
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RDS baseband signal
Plotted in complex plane:
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Plotted in complex plane:
RDS baseband signal
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RDS baseband signal
● RDS binary data is modulated as:– AM: {-1, 1}*ei2πfct → after mixing: {-1, 1}
– “FM” (2PSK): ei2πfct-i{0,π} → after mixing: {-1, 1}
● In the complex plane, the signal should stay on the real axis
● Rotation caused by carrier estimation error,we will compensate for that
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Interpolation and decimation
● RDS symbol rate is 1187.5 Hz * 2 (bi-phase)– Lower than and not a multiple of the sampling rate
● Decimation (skipping samples) and interpolation (reconstructing signal inbetween samples) will return symbols with correct rate and sampling points– Need to know (symbol) clock phase and frequency
→ clock recovery
– Interpolation with first order estimate vs. filter
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Symbol detection
● When the signal stays on the real axis and the symbol timing is correct, detection is easy:
out = 1 when real(symbol) > 0 else out = 0
● Assuming the detection was correct, the angle of the (complex) symbol is a phase error feedback source
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Carrier estimation correction
● The phase error from a detected symbol can be used to correct the phase of further samples– Low-pass filtering (IIR)
● A constant (very low frequency) term in the phase error means frequency error– Use for carrier frequency correction
– Low-pass filtering (IIR)
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Clock recovery
● With a good carrier phase and frequency estimation, the signal has (real) zero crossings in-phase with the bit-clock– Detect zero crossing
– Adjust current clock phase
– Low-frequency term of phase error = frequency error → adjust
● Bi-phase coding (1→10; 0→01)– Zero crossing in every bit
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RDS baseband signal
Without f / θ correction:
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RDS baseband signal
With f correction:
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RDS baseband signal
With f and θ correction:
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RDS baseband signal
After clock recovery, interpolation and decimation:
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RDS baseband signal
Constellation diagram (IQ plot):
But each bit has 2 points (01 = 0; 10 = 1)We should make use of this!
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RDS baseband signal
Constellation diagram (IQ plot),
bi-phase decoded:
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RDS baseband signal
Constellation diagram (IQ plot),
bi-phase decoded – badly:
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RDS baseband signal
Real part of the signal
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RDS baseband signal
Real part of the signal
Black dots are resulting 1s and 0s
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All done!
Source MixerFilter
Decim.Demod
Mixer FilterInterp.Decim.
Symboldet.
Audio
RDS
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Introduction to Algorithmsfor Wireless Communication
LU Hardware Software CodesignWS15/16
Robert NajvirtTU Wien, Embedded Computing Systems Group
Wien, 16. 10. 2015