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Studies on Placement of SemiconductorOptical Amplifiers in Wavelength Division
Multiplexed Star and Tree Topology Networks
by
Yatindra Nath Singh
submitted
in fulfilment of the requirement of degree ofDoctor of Philosophy (Ph.D.)
to
Electrical Engineering DepartmentIndian Institute of Technology, Delhi
Hauz Khas, New Delhi 110016India
September 1996
Certificate
This is to certify that the thesis entitled"Studies on Placement of Semiconductor Optical
Amplifiers in Wavelength Division Multiplexed Star and Tree Topology Networks"being
submitted by Mr. Yatindra Nath Singh to the Department of Electrical Engineering, Indian
Institute of Technology, Delhi is the record of the bonafide research work carried out by him.
He has worked under our supervision and guidance during the period December 1992 to
August 1996. He has fulfilled all the requirements for submission of the thesis which has
reached the requisite standard.
The results contained in this thesis have not been submitted either in part or in full to
any other university or institute for the award of any degree or diploma.
(Prof. Hari Mohan Gupta)
(Dr. Virander Kumar Jain)Thesis Supervisors
Department of Electrical EngineeringIndian Institute of Technology, Delhi
Hauz Khas, New DelhiIndia
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Acknowledgement
I am highly indebted to my thesis supervisors Prof. Hari Mohan Gupta and
Dr. Virander Kumar Jain for giving me the opportunity to work under their supervision. They
had encouraged me in period of distress and anxiety and guided me to accomplish this
research work.
I must acknowledge the staff of optical communication laboratory, IIT Delhi
(Mr. A. P. Thukral, Ms. Neeru Asija and Mr. J. P. Naudiyal) for their support and help during
the research work.
My parents had kept me free from my duties at home so that I can devote more time
to my research work. I acknowledge them for their blessings and support.
My friends Mr. Brejesh Lall and Mr. Bharat Gupta must also be acknowledged for
their patience while listening to me about my research work and for their suggestions and
encouragement.
I sincerely thank all the persons who have helped and supported me directly or
indirectly in the course of this research work.
(Yatindra Nath Singh)
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Abstract
This thesis is mainly concerned with the use of semiconductor optical amplifiers
(SOAs) in wavelength division multiplexed (WDM) broadcast topologies viz. star and tree.
The aim of investigations is to determine the increase in the number of users when SOAs are
placed in the above topologies. Various placement options have been considered in the above
investigations.
Error correcting codes can also be used in optical networks to increase the number of
users by improving the available power budget. Therefore, an on-off keying (OOK)
communication system has been investigated with SOA as preamplifier and an error
correcting code. The coding gain in the single channel point-to-point link has been computed.
In this study, the baseband filter in the receiver is assumed to be optimum for uncoded
system. Hence, the coding gain in the above includes the effect of increased intersymbol
interference (ISI). It is compared with the gain obtained due to placement of SOA in the link.
The suitability of SOA over coding has been discussed based on the above comparison. It is
shown that SOA provides much higher gain than the use of error correcting code.
A detailed study on the use of SOAs in WDM star topology is also carried out. Two
schemes have been considered viz. SOAs as postamplifiers and preamplifiers. In the
postamplifier scheme, SOAs are placed after the transmitter and in the preamplifier scheme
before the receiver. In the postamplifier scheme, three cases have been investigated. First case
corresponds to unsaturated SOAs, second to gain saturated SOAs and in third case effect of
reflection noise is studied. Similarly, in the preamplifier case unsaturated SOAs, average gain
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saturated SOAs with and without gain fluctuations have been considered. Further, reflection
noise is considered as in postamplifier scheme. It is observed that for typical values of system
parameters, SOAs as preamplifiers perform better than the postamplifiers.
The study on placement of SOAs has been extended to WDM tree topology passive
broadcast network i.e. WDM tree-net. The tree-net consists of star as main topology and
folded bus as auxiliary topology. Star portion consists of a star coupler. A tree-net with
b branches usesbxb star coupler. The SOAs can be placed in the star portion of the tree-net
to increase the supportable number of users. However, the number of SOAs can be smaller
than b to support the same number of users as in star. In this study unsaturated SOAs and
average gain saturated SOAs with and without gain fluctuations have been considered. On
comparison with star, it is observed that a tree-net can support more users than a star for a
given number of SOAs.
It is concluded that SOAs as preamplifiers perform better in star topology. When
SOAs are used in tree topology, number of users supported can be more than in star. Further,
the required number of SOAs would be lesser in tree than in star for a given number of users.
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Table of Contents
List of Figures ix
List of Tables xiii
List of symbols xv
Abbreviations xix
Chapter 1Introduction 1
1.1 Need for Optical Communications. . . . . . . . . . . . . . . . . . . . . . . . . . . . 11.2 Fiber Optic Networks . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 21.3 Multiplexing Schemes . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 41.4 WDM Broadcast Networks . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 71.5 Thesis Outline . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10
Chapter 2Optical Amplifiers in Broadcast Networks 13
2.1 Optical Amplifiers . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 132.2 Optical Amplifiers in Broadcast Networks . . . . . . . . . . . . . . . . . . . . . 20
2.2.1 Bus . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 202.2.2 Dual Bus . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 222.2.3 Ring . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 232.2.4 Star . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 26
Chapter 3Semiconductor Optical Amplifier and Coding in OOK System 37
3.1 Uncoded System. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 403.2 Coded System. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 433.3 Uncoded System with Optical Amplifier . . . . . . . . . . . . . . . . . . . . . . 453.4 Example . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 483.5 Conclusions . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 49
Chapter 4Semiconductor Optical Amplifiers in WDM Star Topology 51
4.1 System Description. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 524.2 Amplifier Model . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 544.3 Evaluation of Minimum Required Transmitter Power . . . . . . . . . . . . 564.4 Star without Amplifier . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 564.5 Star with Postamplifier . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 59
4.5.1 Unsaturated Amplifiers . . . . . . . . . . . . . . . . . . . . . . . . . . . . 594.5.2 Effect of Gain Saturation . . . . . . . . . . . . . . . . . . . . . . . . . . . 624.5.3 Effect of Reflection Noise. . . . . . . . . . . . . . . . . . . . . . . . . . . 64
4.6 Star with Preamplifier . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 694.6.1 Unsaturated Amplifier . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 70
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4.6.2 Effect of Gain Saturation . . . . . . . . . . . . . . . . . . . . . . . . . . . 704.6.3 Effect of Reflection Noise. . . . . . . . . . . . . . . . . . . . . . . . . . . 75
4.7 Example . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 794.8 Conclusions . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 88
Chapter 5Semiconductor Optical Amplifiers In WDM Tree-net 91
5.1 System Description. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 925.2 Analytical Model . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 965.3 Example . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1005.4 Conclusions . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 107
Chapter 6Conclusions 109
References 113
Appendix - I 123
Appendix -II 129
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List of Figures
Fig.2-1 psds of (i) ASE-signal beat noise, (ii) ASE-ASE beat noise and (iii)ASE-shot noise components. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 16
Fig.2-2 Forward pumped doped fiber amplifier. . . . . . . . . . . . . . . . . . . . . . 18
Fig.2-3 Optical amplifiers in bus topology.. . . . . . . . . . . . . . . . . . . . . . . . . 21
Fig.2-4 Dual bus network using fiber as point-to-point link.. . . . . . . . . . . . . 23
Fig.2-5a Schematic of non-regenerative photonic dual bus (NI is the nodeinterface).. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 23
Fig.2-5b Node interface for head of the bus (node 1).. . . . . . . . . . . . . . . . . . . 24
Fig.2-5c Node interface for node 2 to N.. . . . . . . . . . . . . . . . . . . . . . . . . . . 24
Fig.2-6 Ring network with distributed EDFA.. . . . . . . . . . . . . . . . . . . . . . . 25
Fig.2-7 4x4 star coupler with single EDFA.. . . . . . . . . . . . . . . . . . . . . . . . . 27
Fig.2-8 8x8 coupler based on 4x4 star couplers.. . . . . . . . . . . . . . . . . . . . . . 27
Fig.2-9 Implementation of distributedNu x Nu (Nu=m2) reflective star couplerbased onm number ofm x m couplers. . . . . . . . . . . . . . . . . . . . . . . 28
Fig.2-10 16x16 distributed reflective star coupler.. . . . . . . . . . . . . . . . . . . . . 29
Fig.2-11 Implementation of distributedNu x Nu (Nu= 2 m2) coupler based on 2mnumber ofmxm couplers.. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 30
Fig.2-12 32x32 distributed reflective star coupler.. . . . . . . . . . . . . . . . . . . . . 31
Fig.2-13 FDM/OFDM distributed expandable amplified star couplerconfiguration. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 32
Fig.2-14 Star coupler with amplifiers and without bandpass and bandstopfilters. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 33
Fig.2-15 8x1 coupler based on seven 2x2 couplers.. . . . . . . . . . . . . . . . . . . . 34
Fig.2-16 Forward pumped EDFA.. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 35
Fig.2-17 mmc x mmc reflective star. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 35
Fig.2-18 mc x mc reflective star coupler based onmcx1 tree coupler.. . . . . . . . . 36
Fig.3-1a The system block diagram for optical communication system withcoding scheme.. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 38
Fig.3-1b The system block diagram for optical communication system with SOAas preamplifier.. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 38
Fig.3-2 Worst-case waveform patterns for (a) bit 1 and (b) bit 0 before andafter the Gaussian filter.. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 42
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Fig.3-3 Variations of BER vs received power level (dBm) for (i) uncodedsystem, (ii) coded system without decoding, (iii) coded system withdecoding and (iv) uncoded system with SOA as preamplifier.. . . . . . . 49
Fig.4-1 An 8x8 star coupler consisting of 3 dB 2x2 couplers.. . . . . . . . . . . . 53
Fig.4-2 Star network without optical amplifier.. . . . . . . . . . . . . . . . . . . . . . . 58
Fig.4-3 Star network with postamplifiers (A, B, ...F is echo path).. . . . . . . . . 60
Fig.4-4 Star network with preamplifiers (A, B, ...G is echo path).. . . . . . . . . 77
Fig.4-5 Variations of minimum required average transmitter powerPta withnumber of usersNu for ε = 0.0 in postamplifier scheme. . . . . . . . . . . 80
Fig.4-6 Variations of minimum required average transmitter powerPta withnumber of usersNu for ε = 0.05 in postamplifier scheme. . . . . . . . . . 81
Fig.4-7 Variations of minimum required average transmitter powerPta withnumber of usersNu for ε = 0.10 in postamplifier scheme. . . . . . . . . . 82
Fig.4-8 Variations of minimum required average transmitter powerPta withnumber of usersNu for ε = 0.15 in postamplifier scheme. . . . . . . . . . 83
Fig.4-9 Variations of minimum required average transmitter powerPta withnumber of usersNu for ε = 0.0 in preamplifier scheme. . . . . . . . . . . 84
Fig.4-10 Variations of minimum required average transmitter powerPta withnumber of usersNu for ε = 0.05 in preamplifier scheme. . . . . . . . . . . 85
Fig.4-11 Variations of minimum required average transmitter powerPta withnumber of usersNu for ε = 0.10 in preamplifier scheme. . . . . . . . . . . 86
Fig.4-12 Variations of minimum required average transmitter powerPta withnumber of usersNu for ε = 0.15 in preamplifier scheme. . . . . . . . . . . 87
Fig.4-13 Variations ofPta with ε for different Nu in postamplifier scheme. Solidlines correspond to gain saturated SOAs and dashed lines to gainsaturated SOAs with reflection noise.. . . . . . . . . . . . . . . . . . . . . . . . 88
Fig.4-14 Variations ofPta with ε for different Nu in preamplifier scheme. Solidlines correspond to gain saturated SOAs and dashed lines to gainsaturated SOAs with reflections.. . . . . . . . . . . . . . . . . . . . . . . . . . . 89
Fig.5-1 Basic tree-net topology.. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 92
Fig.5-2a Structure of star coupler in tree-net without amplifiers.. . . . . . . . . . . 93
Fig.5-2b Structure of branches in a tree-net without amplifiers.. . . . . . . . . . . . 94
Fig.5-3a A 4x4 star coupler with one amplifier in tree-net.. . . . . . . . . . . . . . . 94
Fig.5-3b A 4x4 star coupler with two amplifiers in tree-net.. . . . . . . . . . . . . . 95
Fig.5-3c A 4x4 star coupler with four amplifiers in tree-net.. . . . . . . . . . . . . . 95
x
Fig.5-4a Variations ofNu with Na (unsaturated SOAs) forn=2. The values in thebrackets are corresponding requiredPta in dBm. . . . . . . . . . . . . . . . 102
Fig.5-4b Variations ofNu with Na (unsaturated SOAs) forn=3. The values in thebrackets are corresponding requiredPta in dBm. . . . . . . . . . . . . . . . 102
Fig.5-5a Variations ofNu with Na (average gain saturated SOAs) forn=2. Thevalues in the brackets are corresponding requiredPta in dBm. . . . . . . 103
Fig.5-5b Variations ofNu with Na (average gain saturated SOAs) forn=3. Thevalues in the brackets are corresponding requiredPta in dBm. . . . . . . 103
Fig.5-6a Variations ofNu with Na (average gain saturated SOAs with gainfluctuations) forn=2. The values in the brackets are correspondingrequiredPta in dBm. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 104
Fig.5-6b Variations ofNu with Na (average gain saturated SOAs with gainfluctuations) forn=3. The values in the brackets are correspondingrequiredPta in dBm. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 104
Fig.A-1 Reflected and transmitted signals in a Fabry-Perot amplifier.. . . . . . 124
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List of Tables
Table 4-1 Number of users supported in the postamplifier scheme forε=0.10. . . 86
Table 4-2 Number of users supported in the preamplifier scheme forε=0.10. . . . 90
Table 5.1 Number of users and requiredPta for the tree-net without SOAs. . . . 105
Table 5.2 Maximum number of users andPta for a given number of SOAs.Numbers in brackets are the corresponding values ofn. . . . . . . . . . . 107
Table 5.3 Comparison of star network and tree-net in terms of number of SOAsrequired for a given number of users.. . . . . . . . . . . . . . . . . . . . . . 108
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List of symbols
a0(τ) Worst-case waveform for bit 0 in the presence of instersymbol interference(ISI)
a1(τ) Worst-case waveform for bit 1 in the presence of ISI
b Number of branches in the tree-net
bc Bit in the desired channel
br Bit whose echo produces the reflection noise
B Bit rate per user
Be Bandwidth of electrical filter in receiver
Bo Optical filter/demultiplexer bandwidth
Cf Velocity of light in fiber
Dth Decision threshold level
e Electronic charge
eecho Echo signal electric field
er Signal electric field at the receiver
erfc(x)
Ei Input electric field amplitude at Fabry-Perot cavity
Eo Output electric field amplitude at Fabry-Perot cavity
Er Reflected electric field amplitude from Fabry-Perot cavity
g Gain coefficient of SOA
go Unsaturated gain coefficient of SOA
G Amplifier gain
G0 Unsaturated amplifier gain
Gav Average gain of SOA when multiple channels are being amplified
GFP Gain of F-P amplifier
Gp Gain of SOA when signal corresponding to bitbr is amplified
Gp(br) Gain of SOA when signal corresponding to bitbr is amplified
h Planck’s constant
xv
h(τ) Impulse response of electrical filter in the receiver
H(f) Frequency response of electrical filter in the receiver
iecho-sig Echo and signal beat noise current
Isig Signal current at photodetector
k Number of data symbols in a coded block
kb Boltzmann’s constant
L Length of fiber from user to star coupler
Las1 Loss between SOA and splice 1
Lc Coherence length of laser linewidth
Lcp Amplifier coupling loss
Lcv Star coupler variability
Li Insertion loss of 3 dB 2x2 coupler
Lfi Insertion loss of filter or demultiplexer
Lg Length of gain medium
Lsp Fiber splice loss
Lss Distance between two consecutive users on a branch in the tree-net
Lti Total insertion loss of star coupler
Ltr Loss between transmitter and receiver
mc Size of central coupler
M Maximum number of users on a bus segment without SOA
n Number of users per branch in the tree-net
nsp Spontaneous emission factor
N Number of symbols in a block
Na Number of amplifiers
Nu Number of users (stations)
P Optical power
Pe Probability of error
Pes(ad) Probability of symbol error after decoding
Pes(bd) Probability of symbol error before decoding
Pin Input optical power to SOA
Pint Total input power to amplifier
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Pout Output power of SOA
Pr Received optical signal power at the photodetector
Pr(0) Received optical signal power at the photodetector for bit 0
Pr(1) Received optical signal power at the photodetector for bit 1
Pra Average received optical power at the photodetector
Psat Saturation power level of SOA
Pt Transmitted optical power
Pta Average transmitted optical power
Pt(0) Transmitted optical power for bit 0
Pt(1) Transmitted optical power for bit 1
R Data rate
R1 Reflection coefficient of facet 1
R2 Reflection coefficient of facet 2
Ramp Reflectivity of SOA
Rf Facet reflectivity of SOA (Rf = R1 = R2)
RL Receiver load resistance
Ro Responsivity of photodetector
Rsp Reflection coefficient of splice
S0 Signal level for bit 0 at timet=0 for worst-case bit sequence in presence of ISI
S1 Signal level for bit 1 at timet=0 for worst-case bit sequence in presence of ISI
SASE-shot(f) psd of shot noise due to ASE
SN(f) psd of additive Gaussian noise
Sshot psd of shot noise
Ssp Single sided ASE noise psd due to amplifier
Sspi psd of noise at the receiver due toith amplifier in postamplifier scheme in starnetwork
Sth psd of thermal noise
t Number of correctable errors in a coded block
T Absolute temperature in Kelvin
Tamp Transmittance of amplifier cavity
Tb Bit period
Tmax Maximum value ofTamp
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W1 Wavelength band 1 in WDM/FDMA system
α Attenuation coefficient of fiber in dB/km
β Propagation constant of electric field in a given media
ε Extinction ratio
∆ν Laser linewidth
∆νL Longitudinal mode spacing of FP cavity
η Quantum efficiency of photodetector
λ Operating wavelength
λc Wavelength for clock broadcast in photonic dual bus
λd Wavelength for data broadcast in photonic dual bus
λp Pump wavelength
λs Signal wavelength
ν Optical frequency
νm Resonant frequency ofmth peak in FP cavity transmission spectrum
σ2(1) Noise variance for bit 1
σ2(0) Noise variance for bit 0
σ2(bc) Noise variance for bitbc
σ2ASE-ASE ASE-ASE beat noise variance
σ2ASE-shot Shot noise variance due to ASE noise
σ2ASE-sig ASE-signal beat noise variance
σ2n Noise variance
xviii
Abbreviations
ASE Amplifier Spontaneous Emission
BER Bit Error Rate
BPF Band Pass Filter
BSF Band Stop Filter
CDM Code Division Multiplexing
CDMA Code Division Multiple Access
dc Direct Current
DFA Doped Fiber Amplifier
DQDB Distributed Queue Dual Bus
EDFA Erbium Doped Fiber Amplifier
FCS Fiber Channel Standard
FDDI Fiber Distributed Data Interface
FDM Frequency Division Multiplexing
FPA Fabry-Perot Amplifier
FT-FR Fixed Transmitter-Fixed Receiver
FT-TR Fixed Transmitter-Tunable Receiver
HIPPI HIgh Performance Parallel Interface
ISI Inter Symbol Interference
LAN Local Area Network
MAC Media Access Control
MAN Metropolitan Area Network
OA Optical Amplifier
O/E Optical-to-Electronic
OOK On-Off Keying
psd Power Spectral Density
RATO Random Access Time Out
SAN Subscriber Access Network
SDH Synchronous Digital Hierarchy
SOA Semiconductor Optical Amplifier
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SONET Synchronous Optical NETwork
TDM Time Division Multiplexing
TT-FR Tunable Transmitter-Fixed Receiver
TT-TR Tunable Transmitter-Tunable Receiver
TWA Travelling Wave Amplifier
WAN Wide Area Network
WDM Wavelength Division Multiplexing
xx
Chapter 1
Introduction
1.1 Need for Optical Communications
Technical breakthroughs are affecting the human society for ages. It is well known that
discovery of fire, agriculture and wheel has made the human beings superior over all the other
species on the earth. In the last two centuries, industrial revolution started by the invention
of steam engine by James Watt has changed the face of humanity. Nowadays, we are
witnessing information revolution which is affecting the humanity.
Information revolution implies that the information can be presented, analyzed,
transported in an efficient manner. Computers are facilitating the presentation and analysis
of information, while the transportation of information is achieved using communication
networks. With the passage of time, communication networks are becoming independent of
type of information. Now, the information moving over the networks can be voice, video,
computer data or text. The networking for supporting such information is termed as
multimedia networking. Multimedia networks are designed to carry a large amount of
information bits per second. The high bit rates are especially needed by the upcoming high
bandwidth real-time video services [58] (e.g. video conferencing and video on demand). At
present, optical fiber is the only transmission medium offering such large bandwidth
[27, 28, 39]. Optical fiber also provides the low loss communication links as compared to
1
radio or electrical cables. In addition to large bandwidth and low loss, there are many other
advantages of using optical fiber. Optical fibers are immune to electromagnetic interference;
comparatively lighter and cheaper than copper cables required to carry the same amount of
information. As the transmission of information is through dielectric media, transmitting and
receiving ends are electrically isolated. Optical links are more reliable and can support future
application due to inherently large available capacity.
Optical fiber links are best suited for fixed user locations. These links require
specialized tools and skills for installation and maintenance. Further, the technology of optical
devices and components, especially optical sources and detectors is still evolving to match
the system requirements.
Optical fiber is finding increasing use in the communication networks due to above
advantages [42]. The telecommunication service providers have laid down the optical fiber
links on the land and in the oceans for trunk traffic. Optical fibers are finding increasing use
in subscriber loop too [20, 43, 52, 65, 85, 95]. It is also used in computer networking [6, 66].
1.2 Fiber Optic Networks
Optical fiber has found use in switched communication networks by replacing the
other media viz. microwave, electrical cable. Nowadays, almost all the trunk lines of existing
networks are using optical fiber. This large scale use of optical fiber has led to the
development of synchronous digital hierarchy (SDH)/ synchronous optical network (SONET)
standards for switched networks [35, 73, 82]. In future, the link between the user and the
2
switch i.e. subscriber loop will also be based on fiber. Consequently, new services (e.g.
videophony, video on demand) can be made available by telecommunication service providers.
The fiber has also replaced the media in the broadcast and select networks which are
commonly used as local area networks (LANs). Consequently, ethernet, token bus and token
ring have been implemented on optical fiber. As the fiber is used to replace conventional
media, these networks should be designed to harness the full fiber capabilities. The broadcast
networks can be classified as active or passive. When the signal is optoelectronically
regenerated or amplified, the network is active broadcast network otherwise it is passive
broadcast network. Ethernet and token bus are the examples of passive broadcast network,
while token ring is of active broadcast network. In passive broadcast networks, the transmitted
optical power is split for distribution among the receivers. Therefore, increase in number of
users implies that each receiver will receive reduced amount of optical power for a fixed
transmitted power level. The reduction in received optical power level will worsen the
receiver performance. To keep the receiver performance acceptable, the number of users have
to be limited. Such a limitation on number of users does not exist in active broadcast
networks, but the active broadcast networks suffer with other problems e.g. low reliability,
higher cost etc..
New networks e.g. fiber distributed data interface (FDDI) [25, 26, 74] and distributed
queue dual bus (DQDB) have also been deployed with optical fiber as media. These networks
operate at higher bit rates and cover larger distances. FDDI uses ring topology. It contains
two counter propagating rings for high reliability. In case of failure of a node or a link, the
fault is bypassed using the other ring. DQDB uses dual bus or dual ring as topology. Each
3
of the two bus or ring is unidirectional and carries data in opposite directions. In the above
networks, optical fiber is used as point-to-point link connecting two consecutive nodes.
However, it is possible to use fiber as passive broadcast media by using passive taps in
DQDB network. These networks operate at bit rates of the order of 100 Mb/s due to optical
media. The network standards with still higher bit rates (of the order of Gb/s) have been
developed e.g. fiber channel standard (FCS) and high performance parallel interface (HIPPI).
HIPPI uses multiple parallel links, each of which is operating at bit rates of the order of 100
Mb/s. The parallel links can use electrical cable for shorter distances (few meters) or optical
fiber for longer distances (few kms). Further increase in capacity of broadcast networks for
efficient utilization of optical fiber has been hindered by electronic bottleneck. The transmitter
and receiver become extremely costly with the increase in bit rates above Gb/s. At high bit
rates, optical multiplexing and demultiplexing techniques are used to attain large capacity
networks. Large capacity switched optical networks are also possible [34, 93]. In these
networks, many switches are interconnected. The signal remains optical from transmitting to
receiving end. Therefore, switching is optical in nature and optical multiplexing and switching
techniques will be used for increasing the capacity [2].
1.3 Multiplexing Schemes
The bandwidth requirement is expected to increase with time. Therefore, research in
optical fiber networks is directed towards attaining high capacity optical networks. As
mentioned above, high capacities in these networks can be achieved by using various
multiplexing techniques. There are three possible approaches: (i) wavelength division
4
multiplexing (WDM), (ii) time division multiplexing (TDM) and (iii) code division
multiplexing (CDM). Combinations of the above can also be used.
A WDM system is similar to frequency division multiplexed (FDM) radio broadcasting
system. The optical spectrum is sliced in multiple channels centred at different wavelengths
[8, 9, 53, 77, 78, 79]. Ideally, the information in various channels do not interfere with each
other. However, interchannel interference may occur when the information passes through
optical amplifiers (OAs) or any other nonlinear device in the link. Implementation of WDM
systems require couplers [69], wavelength multiplexers and demultiplexers, tunable or fixed
wavelength sources and detectors capable of operating over the entire wavelength range. Also
the various parameters characterizing the OAs, couplers, fibers etc. are desired to be uniform
in the operating wavelength range. There are many issues which must be tackled in a WDM
system. Two of these are: (i) wavelength stability of sources and (ii) channel spacing. If the
transmitter source wavelength is not stable, it may drift towards the neighbouring wavelength
channels. Consequently, channels spacing will reduce resulting in crosstalk. Various
wavelength stabilizing schemes have been proposed to avoid drift [70]. Most of these schemes
compare the transmitting wavelength with a reference and adjust the transmitting source
wavelength continuously. Channel spacing is an important issue [81]. Smaller spacing implies
more channels in a given spectral range. But the demultiplexers resolution decides the
spacing. For smaller channel spacing, narrow bandwidth filters are required. When coherent
receivers are used, channel spacing can be very small (2 to 4 times the signal bandwidth) as
compared to when noncoherent receivers are used [10, 11]. The WDM systems with a smaller
channel spacing are termed as optical FDM systems [33].
5
In TDM systems, optical pulses from various sources carrying the information are time
multiplexed [4, 41]. In these systems, the pulse width reduces with the increase in number
of users when bit rate per user is fixed. It must be≤ 1/(Nu·B) whereNu is number of users
andB the bit rate per user. Such a system requires the optical sources which generate very
narrow width optical pulses. Generally, mode locked lasers can be used for this purpose. The
output of these are then externally modulated depending upon the information to be
transmitted. If internal modulation is used on commonly used laser sources, pulse compression
has to be applied to generate narrow pulses. Such a compression is generally achieved using
nonlinear processing. In optical TDM, the pulses from various sources require very tight delay
adjustment so that pulses can be multiplexed together. Further, exact timing information is
required at all the receivers for demultiplexing [3] which can be obtained by centralized clock
or synchronized distributed clocks. Therefore, implementation of optical TDM system requires
tight clock jitter control and clock synchronisation at very high frequencies (≥ 1 THz).
In CDM systems, each user is assigned a unique waveform code to represent the
information bit [1, 21, 51]. The codes are selected in such a manner that code sequence of
each user has very small correlation with code sequences of all the other users. Thus codes
are equivalent to independent channels. At the receiving end, optical correlators are used for
identifying the information destined for it. As the number of waveform codes are equal to
number of users, increase in number of users implies more number of pulses in waveform
code for a bit. Consequently, for a given bit rate the pulse width will decrease with the
increase in number of users. In a code division multiple access (CDMA) broadcast network
having more than 100 users, bit rate of 1 Gb/s per user implies pulses of the order of
10 picoseconds. These short pulses can be generated by a mode locked laser. With these
6
narrow pulses and proper optical delay lines, suitable waveform code can be generated [40].
At the receiver end, delay lines are used to decode the required waveform. In a broadcast
situation either encoders or decoders or both can be tunable. Each waveform code is used as
an independent channel. In encoders and decoders, optical fiber delay lines which require tight
fiber length tolerances are used. To make the delay lines, tunable switching can be used. Fine
tuning of delay can be achieved using Piezoelectric tuning of delay lines.
It may be mentioned that for implementing a WDM system, fixed/tunable sources,
wavelength multiplexers and demultiplexers and fixed/tunable receivers are required. These
devices are available at the current state of the art technology [5, 15, 16, 29, 56].
In comparison, implementation of encoders/decoders and time multiplexers/demultiplexers at
Tb/s is very difficult. Therefore, WDM implementation is comparatively easier than that of
TDM and CDM [13]. It is expected that WDM switched as well as broadcast networks will
dominate the future for quite some time. As WDM systems can provide large bandwidth,
complexity of switched network can be avoided by using broadcast network topologies.
1.4 WDM Broadcast Networks
Many issues must be investigated for implementing a WDM broadcast network. Some
of the important issues are: (i) topology, (ii) tunability characteristics of transmitter,
(iii) tunability characteristics of receiver, (iv) size of the network, (v) number of channels and
(vi) media access control protocols. Some issues are inter related also.
7
Fiber layout to connect the different users constitute the physical topology of the
networks [66]. A physical broadcast topology must have some desirable features. A few of
these are given below.
(i) In a WDM system, there must be large number of users in the topology to utilize the
available bandwidth. Ideally, each receiver must receive minimum required power for
a given bit error rate (BER) to maximize the number of users supported. A topology
must also provide each receiver with equal amount of power so that receivers with
smaller dynamic range can be used. Sometimes, equal distribution of power can also
lead to more number of users (e.g. star topology supports more users than the bus).
(ii) Fiber used in the network topology must be minimum. This is an important cost
consideration.
(iii) Transmitter to receiver loss within the topology must be minimum. This would mean
more power is available to receivers. Therefore, number of users in the network can
be increased.
(iv) Topology must be extendible. It means that number of users can be increased easily.
When the above is not met, the topology is designed for more number of users than
actually present. The unused ends are latter assigned to the new users. It is also
desired that media access control (MAC) protocol is independent of number of users
in the network.
8
(v) WDM optical network are generally very high speed networks [12]. In such networks,
transmission time is much less than the propagation time. Therefore, the average
propagation time in the network must be minimized while selecting a topology. This
is extremely important for better performance.
(vi) Minimization of number of couplers, multiplexers and demultiplexers, transmitters and
receivers and optical amplifiers in the network topologies is also required. This is an
important cost reduction measure in a large network.
In the broadcast network topologies, star, bus, tree or ring can be used. Among these,
star is the best option as it can support maximum number of users for a given power budget.
The reason for the above is uniform distribution of transmitted power by a star coupler.
In WDM networks, efficient methods (i.e. MAC protocols) for accessing the
bandwidth are desired [31, 36, 44, 45, 60, 64, 71, 103]. In these protocols, contention for the
wavelength channels to be used and time when the packet is to be transmitted are resolved.
There are several possibilities depending on the tunability of transmitters and receivers. One
can have fixed transmitter - fixed receiver (FT-FR), fixed transmitter - tunable receiver
(FT-TR), tunable transmitter - fixed receiver (TT-FR) and tunable transmitter - tunable
receiver (TT-TR). The protocols for the cases when tunable components are used are required
to take into consideration the tuning range and tuning time of the tunable components. When
the tunable range of components is small, it may not be possible to implement the MAC
protocol on all the channels simultaneously. Therefore, the protocol needs to be modified
depending upon the number of channels covered by the tunable range.
9
High capacity WDM networks [97] should be able to support large number of users.
At the current level of technology, the broadcast optical networks support very few users
(≤ 64 users). The number of users can be increased by (i) increasing the power budget,
(ii) reducing the loss in the network, (iii) using the opto-electronic regenerators and (iv) using
optical amplifiers (OAs). The available power budget can be improved by using transmitters
with higher power sources and receivers with better sensitivity. Higher transmitter power and
better receiver sensitivity need improvement in device technology. The error control coding
can be used to provide coding gain and hence the improvement in the receiver sensitivity
which in turn increases the available power budget [38]. Coding techniques require the
encoder and decoder blocks in the transmitter and receiver respectively. The reduction of loss
in the network requires the improvement in splicing techniques and optical components. The
optoelectronic regenerators involve optical-to-electronic (O/E) conversion and vice-versa. This
reduces the reliability of the network as the regenerator is an active device. Further, the
upgradation of multichannel WDM network will require separate regenerator for each channel.
In contrast to the above, an optical amplifier can amplify multiple WDM channels.
1.5 Thesis Outline
This thesis is mainly concerned with the use of semiconductor optical amplifiers
(SOAs) in WDM broadcast topologies viz. star and tree. The aim of investigations is to
determine the increase in the number of users in the above topologies when SOAs are placed.
Further, various SOA placement options are studied. In chapter 2, the characteristics and
suitability of SOAs in networks has been reviewed. The relevant SOA model and parameters
have been presented.
10
In chapter 3, the improvement in an on-off keying (OOK) communication system due
to coding and semiconductor optical preamplifier has been investigated. The coding gain in
the single channel point-to-point link has been computed. In this study, the baseband filter is
assumed to be optimum [37] for uncoded system. Hence, the coding gain in the above
includes the effect of increased intersymbol interference (ISI). It is compared with the gain
obtained due to placement of SOA in the link. The suitability of SOA over coding has been
discussed based on the above comparison [91, 92, 96, 99, 102].
Chapter 4 contains a detailed study on the use of SOAs in WDM star topology. Two
placement schemes, postamplifier and preamplifier, have been considered. In the postamplifier
scheme, SOAs are placed after the transmitter and in the preamplifier scheme before the
receiver. In the postamplifier scheme, three cases have been investigated. First case
corresponds to unsaturated SOAs, second to gain saturated SOAs and in third case reflection
noise is incorporated. Similarly, in the preamplifier scheme unsaturated SOAs and average
gain saturated SOAs with and without gain fluctuations have been considered. Further, the
effect of reflection noise is also investigated like in postamplifier scheme [98, 100].
In chapter 5, the study on placement of SOAs is extended to WDM tree topology
passive broadcast network i.e. WDM tree-net. The tree-net consists of star as main topology
and folded bus as auxiliary topology. Star portion consists of a star coupler. The deployable
number of SOAs has been investigated in the tree-net. This number varies from 1 tob, where
b is number of branches in the tree-net. In this study, unsaturated SOAs and average gain
saturated SOAs with and without gain fluctuations have been considered [101].
11
In chapter 6, conclusions of the thesis are presented. The limitations and shortcomings
of approach in the thesis are discussed. Further possibilities of research and extensions have
been suggested.
12
Chapter 2
Optical Amplifiers in BroadcastNetworks
Optical amplifiers (OAs) can increase the number of users supported by a broadcast
network. Many investigations have been carried out to increase the network size using OAs.
The work reported in this chapter has resulted in the following publication
1. Y. N. Singh, V. K. Jain and H. M. Gupta, "WDM Data Network," Presented inIXth NationalConvention of Electronics and Telecommunication Engineers, University of Roorkee, Roorkee,India, March 30-31, 1994.
Some of the schemes are based on semiconductor optical amplifiers (SOAs) and others on
doped fiber amplifiers (DFAs). This chapter consists of review of OAs in broadcast
networks. Section 2.1 describes operational principles of OAs. Various types of OAs are
compared in this section. Specifically, SOAs are modelled for their subsequent analysis in
networks. The effectiveness of OAs in various schemes, as reported, has been discussed in
section 2.2.
2.1 Optical Amplifiers
Optical amplifier is a device which amplify the input optical signal. This device
works on the principle of stimulated emission [7]. There are two types of OAs which are
used in communication system; (i) semiconductor optical amplifiers (SOAs) and (ii) doped
13
fiber amplifiers (DFAs). The SOAs are basically semiconductor lasers which operate below
lasing threshold [7]. These devices require population inversion so that stimulated emission
and hence amplification can take place. The population inversion is achieved by means of
electrical energy. A SOA has two facets and reflectivities of these facets decide whether
the device will operate as a SOA or a semiconductor laser. When the facet reflectivities are
zero, input signal passes through the device only once. Such an amplifier is called travelling
wave amplifier (TWA). When reflectivities are non-zero but quite small, the signal passes
through the cavity several times. The signal within the cavity reduces with the successive
passes and dies out ultimately. This type of SOA is called Fabry-Perot amplifier (FPA).
In SOAs, gain of amplifier reduces as the input signal power increases. This
phenomenon is called gain saturation. The gain coefficientg is given by [30]
(2.1)
where g0 is the unsaturated gain coefficient,Psat the saturation power level,P the optical
power to the amplifier. The rate of increase of optical power with distance is given by
(2.2)
14
For a TWA, the output power is obtained by using Eqn.2.1 in Eqn.2.2 and integrating
Eqn.2.2 from 0 toLg with initial condition P(0)=Pin, whereLg is the length of gain medium
and Pin the input optical power to SOA. The output power is obtained as
(2.3)
whereG0 (= exp (g0L)) is unsaturated amplifier gain. The amplifier gainG (=Pout/Pin) from
the above equation is given by
(2.4)
A semiconductor laser amplifier alongwith the amplified signal, also produces
amplified spontaneous emission (ASE) noise. It is modelled as a white Gaussian noise with
single sided power spectral density (psd) [30]
(2.5)
where nsp is the spontaneous emission factor,h the Planck’s constant andν the optical
frequency. Typically, the unsaturated gain,G0, of SOAs is in the range 8 - 29 dB and the
Psat in the range 3.1 - 15.6 dBm. The noise figure for SOAs ranges from 6 to 8.5 dB which
corresponds tonsp of 2 - 3.5 [19, 47, 62, 87]. When the amplified signal and accompanying
ASE noise are made to incident at the photodetector, the noise beats with itself and also
with the signal. Thus ASE-ASE and ASE-signal beat noise components are produced. The
15
psds of the above noise components and ASE shot noise which arises due to dc component
of ASE-ASE beat noise are shown in Fig.2-1 [63]. In this figure,Bo is the bandwidth of
optical filter used for limiting the ASE noise of OA,Ro the responsivity of photodetector
and Pr the received optical power level at the photodetector.
Fig.2-1 psds of (i) ASE-signal beat noise, (ii) ASE-ASE beat noise and (iii) ASE-shotnoise components
In a FPA, the gain is given by [30]
(2.6)
In the above equation,R1 and R2 are the facet reflectivities,G(ν) the gain spectrum when
the reflectivities are zero,∆νL the longitudinal mode spacing andνm the resonant
16
frequencies for the cavity. When the FPA can be approximated as TWA
[30].
In DFAs, optical fiber core is doped by rare earth elements e.g. erbium [17, 18, 55],
praseodymium [48, 88] etc.. These amplifiers like SOAs also use stimulated emission for
amplifying the optical signals. In contrast to SOAs, population inversion in these amplifiers
is achieved by optical pumping. The basic scheme for optical pumping is as shown in
Fig.2-2. A coupler is used for combining the information signal and the pump signal. When
these signals travel in a doped fiber, power at the pump wavelengthλp is absorbed and it
creates population inversion. The signal atλs, the signal wavelength, amplifies as it passes
through the doped fiber core having population inversion. The pump power is generated by
semiconductor laser diodes at suitable wavelengths (e.g. 980 nm and 1480 nm for EDFAs).
In Fig.2-2, both pump and information signals propagate in the same direction. Such type
of pumping scheme is called forward pumping. It is possible to introduce the pump power
at the second coupler so that pump and information signal travel in the opposite direction.
This pumping scheme is referred as backward pumping. Both types of pumping can also
be used simultaneously and referred as bidirectional pumping. As the pump power reduces
along the propagation direction, the population inversion also reduces. The signal
amplification depends upon the population inversion profile along the length of doped fiber.
For higher amplification, more population inversion is desired over the larger length. For
a given population inversion profile, there is an optimum length of doped fiber which
maximises the overall gain [30].
17
The relaxation time of excited ions/atoms is an important parameter in determining
Fig.2-2 Forward pumped doped fiber amplifier
the effect of gain variations on the incoming information signal. In DFAs, it is of the order
of few milliseconds. Therefore, signal for both bit 1 and 0 experiences same amplifier gain
when very high bit rate signals are amplified. In contrast to this, the relaxation time in
SOAs is of the order of few nanoseconds. This means that at high bit rates (≈109 b/s), gain
for bit 1 and 0 would be different. Due to this reason, fluctuations in gain for bit 1 and 0
are more in SOAs than in DFAs. This results in comparatively less cross-saturation effect
in DFAs. The cross-saturation effect means the reduction of gain in desired channel due to
the presence of other channels when wavelength division multiplexed (WDM) signals are
amplified by OAs.
The DFAs can be used as in-line component in fiber optic links because these can
be easily spliced with the fiber. Consequently, there is smaller coupling loss. The signal
polarisation does not affect the gain of these amplifiers because of their circularly
symmetric cross-section. In SOAs, there is a large coupling loss (≈3.5 dB/facet typically)
and gain varies with input signal polarisation. The gain sensitivity to signal polarisation in
SOAs can be reduced by using various techniques [30, 89]. SOAs have two distinct
18
advantages over doped fiber amplifiers. These are: (i) SOAs can be easily integrated in
integrated optic transmitter/ receiver and (ii) SOAs are available over a wide wavelength
range (0.8 µm - 1.55 µm).
The most significant application of optical amplifiers is for amplifying the optical
signals in communication links. This increases the regenerator spacing in power budget
limited optical fiber links. In fiber optic broadcast networks, the transmitter power is
distributed among all the users. The number of users are restricted by the transmitter power
level. Use of OAs will increase the available power budget and hence the number of users
supported. This aspect of SOAs has been considered in detail in the following chapters of
the thesis.
In a point-to-point link, OA can be used as (i) postamplifier, (ii) preamplifier and
(iii) in-line amplifier. Postamplifier implies that an OA is used just after the transmitter. It
is also possible that OA is integrated with the source to form a high power optical source.
In this application, OA with higher saturation power is desired to reduce the effect of gain
saturation. DFAs can be used for this application because of their high saturation power
level. However, such a high power optical source would be very bulky. When an optical
amplifier is used as preamplifier, it is placed just before the receiver. This can also be
integrated with the receiver to form a high sensitivity receiver module. The OAs in this
application must produce low noise. Higher value of saturation power level is not required
as in postamplifier. In-line amplifiers are used in the optical fiber link itself [23, 24, 49,
80]. DFAs are better suited for this application because these can be easily spliced in the
link. Remote pumping can also be used to avoid electrical supply to the amplifier.
19
2.2 Optical Amplifiers in Broadcast Networks
As mentioned above, OAs can be used in passive broadcast networks for increasing
the number of users supported. The number of OAs in a network should be minimum for
a given number of supportable users. Conversely, number of supportable users must be
maximized for a given number of OAs. The optimal utilization of OAs can be achieved by
(i) proper placement of OAs in a given network topology and (ii) modifying the existing
topologies to utilize the OAs effectively. In view of the above, many studies have been
made to investigate the effectiveness of OAs in various topologies e.g. bus, ring, star and
some multilevel topologies. In the following, above studies and their results are reviewed.
2.2.1 Bus
Bus topology is very popular in copper based networks. It requires less copper cable
as compared to other topologies. Further, standard media access protocols e.g. IEEE 802.3
can be used. When the bus is implemented on optical fiber, there is a limitation on the
number of users supported by it. This is because of non-uniform distribution of power
among the users, requiring large dynamic range for the receivers. With limited dynamic
range, number of users are limited on bus network.
Bus topology supports very few users (typically < 20) [84]. The optical amplifier
can be used to keep the distribution of received power level more uniform. This results in
increase in supportable number of users. Wagner [84] has considered the use of SOAs in
a single channel bus network with uniformly distributed users. The SOAs are assumed to
20
be placed such that there areM users in between as shown in Fig.2-3. The maximum value
of M depends upon the dynamic range of received and transmitted power levels. It is equal
to number of users which can be supported by the bus without any SOA.
Fig.2-3 Optical amplifiers in bus topology.
There are two factors which limit the increase of number of users when SOAs are
used: (i) ASE noise and (ii) gain saturation. Initially, only the effect of ASE noise is
studied assuming the SOAs to be unsaturated. When a signal passes through many SOAs,
the ASE noise accumulates and degrades the system performance. It limits the number of
SOAs and hence number of supportable users. When the gain saturation is considered,
accumulated ASE noise saturates the SOAs alongwith the signal. This further reduces the
number of supportable users.
Use of heterodyne detection alongwith SOAs has also been studied [84]. In the
study, it is considered that in each section havingM users and a amplifier, end-to-end
signal gain compensates the loss. Therefore, whatever signal power enters in a section also
emerges out of the section. To study the degrading effect of gain saturation, gain saturation
due to last amplifier is considered and for all other amplifiers the gain equal to the loss is
21
assumed. With this assumption, the study gives an upper bound on number of users. The
analysis is limited to single channel bus. It can be modified for a WDM network.
2.2.2 Dual Bus
Dual bus topology is used for implementing distributed queue dual bus (DQDB)
metropolitan area networks (MANs). It consists of two buses which carry data in opposite
direction. The data is transferred in time slots which are generated by the Head of the Bus
(HoB). The two buses use optical fiber for connecting the two consecutive nodes on the
bus. The fiber is basically used as point-to-point link (Fig.2-4). This network has a
disadvantage of being unreliable as it does not use passive bus over the whole network. It
can be made reliable by connecting the nodes to the passive bus using 2x2 couplers. This
limits the number of nodes which can be supported by the network. Study on the use of
OAs in such a passive dual bus for increasing the number of nodes has been carried out
[50]. The above scheme is shown in Fig.2-5. Two wavelengthsλc and λd are used in this
scheme (Fig.2.5b and 2.5c). The wavelengthλc is used to broadcast the clock signal and
λd to transmit/receive the data. As the network is to operate at 10 Gb/s, broadcast of clock
signal on λc is essential. This is because at such a high bit rate, clock recovery and
synchronisation is very difficult. Use of clock atλc and data atλd, requires phase delay
compensation to compensate for smaller phase delays due to environmental variations (e.g.
temperature). The type of OAs although not specified have been modelled for noise and
gain saturation as in SOAs. It has been shown that a photonic dual bus using OAs (with
unsaturated gain of 12 dB and saturation power level of 4 dBm) with 100 nodes spanning
22
hundreds of kilometres is possible. Therefore, such a network is suitable as wide area
network (WAN) or MAN.
Fig.2-4 Dual bus network using fiber as point-to-point link.
Fig.2-5a Schematic of non-regenerative photonic dual bus (NI is the node interface).
2.2.3 Ring
Optical fibers have been used for connecting consecutive nodes in rings. Fiber
distributed data interface (FDDI) is such a ring network designed with fiber as the
23
transmission medium [25, 26]. Ring has also been proposed for self healing synchronous
Fig.2-5b Node interface for head of the bus (node 1).
Fig.2-5c Node interface for node 2 to N.
optical network (SONET) architectures. In these self healing rings, reliability is increased
by creating alternate paths and providing isolation of faulty links. FDDI uses two counter
rotating rings. It employs a loopback mechanism for high reliability in case of node failures.
Passive optical rings can provide high reliability because failure of a node does not break
the ring. But these have power budget problem limiting the number of nodes which can be
24
used on it. This problem can be overcome to a great extent by using optical amplifiers. A
passive ring having distributed erbium doped fiber amplifier has been proposed [22]. The
scheme is shown in Fig.2-6. In the analysis of this ring structure,g/α is considered to be
a constant along the ring. Here,g is gain coefficient andα the attenuation coefficient of
the fiber in the ring. It was shown that wheng is less thanα, ASE noise psd within the
ring attains a constant value which is quite low even whenα-g << 1. Thus distributed
optical amplification can be used in the ring to increase the supportable number of users.
It has been shown that a 300 km ring at 2.5 Gb/s cannot support a single user without
amplifier, but with the distributed amplification over 450 users can be supported. In the
study, quite a few assumptions have been made. Pump power is assumed to cause such a
population inversion profile thatg/α is constant. Some other factors which restrict the
number of users are ignored e.g. (i) dynamic range of receivers, (ii) back reflection at
various points and (iii) remnants of recirculating optical signals.
Fig.2-6 Ring network with distributed EDFA.
25
2.2.4 Star
Ideally, star topology distributes optical power equally at output ports. Therefore, it
can support maximum number of users without OAs as compared to any other topology.
At the present level of technology, number of users supported by star is small (typically
≤ 64). Many modified topologies which use star couplers and OAs have been proposed
[59, 94, 104]. These can support higher number of users as compared to a passive star
topology. The star topology can use either transmissive or reflective stars or both. In
reflective star coupler, input and output ports are same. The user transmits the signal in a
given port and receives the signal from all other users from the same port [67]. The
propagation direction of transmitted and received signals are opposite in the port. Two
schemes of distributed reflective star couplers which use the erbium doped fiber amplifiers
(EDFAs) have been proposed [94]. In both the schemes, 4x4 couplers having an EDFA as
shown in Fig.2-7 is used as basic element. An 8x8 star coupler can be made using 4x4
couplers and 2x2 couplers as shown in Fig.2-8. In the same manner, star coupler of larger
size can be made using smaller size couplers. In the first scheme (Fig.2-9),m number of
mxm star couplers are used. Implementation of eachmxm coupler requirem/4 EDFAs and
6m/4 + (m/2) log2(m/4) number of 2x2 couplers [94]. It can be seen from Fig.2-9 that
reflective star made ofm number ofmxm star couplers can supportNu=m2 number of users.
One output port of each coupler is terminated with a mirror and other (m-1) ports are
connected to remaining (m-1) number ofmxm couplers. A 16x16 distributed reflective star
coupler based on this scheme is shown in Fig.2-10
26
In the second scheme (Fig.2-11), 2m number ofmxm couplers are used to implement
Fig.2-7 4x4 star coupler with single EDFA.
Fig.2-8 8x8 coupler based on 4x4 star couplers.
a distributed reflective star coupler which can supportNu=2m2 number of users [94]. The
mxm couplers are being grouped to formm pairs. In each pair, one output of eachmxm
coupler is connected using 2x2 reflective star coupler. Each pair ofmxm couplers is
connected to every other pair by a 2x2 coupler. A 32x32 reflective star coupler based on
this scheme is shown in Fig.2-12. In these star couplers, less fiber is required as compared
27
Fig.2-9 Implementation of distributedNu x Nu (Nu=m2) reflective star coupler based onm number ofm x m couplers.
28
to a centralized star coupler. The EDFAs are shared by all the users. In the above
Fig.2-10 16x16 distributed reflective star coupler.
proposition, no mention has been made regarding the utility of this star in a WDM system.
The use of above star in a WDM system will require wide bandpass filters in EDFAs.
Further, the required gain of EDFAs for a given number of users is not given, which is
needed in design of such systems. Also the injection of pump in EDFAs will require
wavelength selective coupler.
Another star coupler configuration using EDFAs for WDM/FDMA network
(Fig.2-13) has also been proposed [59]. WDM/FDMA network means that the signal
spectrum consists of many frequency band at different wavelengths. Each band contains
many channels which are wavelength multiplexed with very narrow spacings. In this
29
scheme, there is one central coupler of dimensionmcxmc. All other couplers are auxiliary
Fig.2-11 Implementation of distributedNu x Nu (Nu= 2 m2) coupler based on 2m numberof mxm couplers.
couplers. There aremc wavelength bands and a unique wavelength band is allocated to the
users on auxiliary coupler. Each wavelength band has multiple channels to be used for
transmission by the users on the corresponding auxiliary coupler. When a user on auxiliary
coupler AC1 transmits the signal on a wavelength channel in the assigned bandW1, it is
broadcast to all the users on the same coupler. A part of the signal is transmitted to central
coupler. At the input, only the wavelength bandW1 is allowed to pass through by means
of an optical bandpass filter (BPF). This filter allows only the signals from users on AC1
30
to be passed, which are then amplified and broadcast to the other auxiliary star couplers.
Fig.2-12 32x32 distributed reflective star coupler.
The output fiber connected to AC1 from central star contains a bandstop filter (BSF) for
wavelength bandW1. Ideally, the use of BSF prevents the recirculation of the optical signal
in wavelength bandW1. One of the output ports ofmcxmc central coupler can be used as
the input for the pump power for all the EDFAs. This scheme has the advantage that
existing networks on auxiliary stars are easily interconnected. The network size is easily
expandable by using auxiliary stars until all the ports of the central star are filled. Sharing
of pump source, amplification of a part of spectrum by EDFAs are the main features of the
scheme. The disadvantage is that recirculating signals can produce interference in practical
BSFs. The interference can be minimized by suitably matching the BPFs and BSFs. The
31
mxm star coupler must be wideband as the pump signal also traverse through the central
coupler.
Fig.2-13 FDM/OFDM distributed expandable amplified star coupler configuration.
A few other configurations using star couplers with OAs have been reported [59,
104]. The star coupler proposed in [59] uses BPFs and BSFs for each wavelength band.
This coupler is modified by Yung-Kuanget.al [104] and the modified version is shown in
Fig.2-14. This is ammcxmmc centralized star coupler. The 1xmc and mcx1 couplers can be
made using (mc-1) number of 2x2 couplers as shown in Fig.2-15. Themcxmc coupler is a
transmissive star coupler made using (mc/2)log2(mc) number of 2x2 couplers. Each OA is
a forward pumped EDFA as shown in Fig.2-16. This scheme supports more number of
users thanm(mc-1)xm(mc-1) coupler [59]. The number of required 2x2 couplers is less than
32
that of star coupler [59] form ≥ 32. This coupler does not require dedicated BPF and BSF
as in [59].
Fig.2-14 Star coupler with amplifiers and without bandpass and bandstop filters.
As each user must be connected to the centralized star coupler, there is a large fiber
requirement. The loss between transmitter and receiver is more than the loss in the coupler
with BPFs and BSFs. The fiber requirement can be reduced by making the above star
coupler distributed. This can be achieved by putting the 1xm and mx1 couplers with the
group of m users. It implies that fiber is required only to connect the 1xm and mx1
couplers tomcxmc star. This saves the required fiber as well as the required conduit length
for fiber layout. Further, the number of 1xm couplers can be reduced by using reflective
mcxmc star coupler. The resultingmmcxmmc coupler is shown in Fig.2-17. The above
modification also reduces the required fiber to half as the transmitted signal and signal to
33
be received share the same fiber in opposite direction. These signals can be separated by
using diplexers at the user ends. Themcxmc reflective star coupler can be made by using
a mcx1 coupler whose single port is terminated by a mirror (Fig.2-18). There are also two
other possible ways to form amxm reflected star coupler. These are shown in Figs.2-9 and
2-11.
Fig.2-15 8x1 coupler based on seven 2x2 couplers.
In all the above studies, degrading effects due to OAs have not been considered.
Therefore, these give an upper bound on the supportable number of users. In some of the
studies, new schemes have been proposed which use the OAs more efficiently. But their
practical implementation require some special devices e.g. mirrors for terminating the ports
and 2x2 reflective star couplers.
34
An accurate analysis is needed to compute the supportable number of users which
Fig.2-16 Forward pumped EDFA.
Fig.2-17 mmc x mmc reflective star.
is expected to be lower than the upper bound. Therefore, the previous performance bounds
cannot be used to compare the various schemes. Only a qualitative comparison can be
made. All recent studies are mostly based on EDFA due to its popularity. It is remarked
that the doped fiber can only be used in distributed star coupler or in bus and ring
35
networks. In centralized star couplers, SOAs can be easily integrated with integrated optic
Fig.2-18 mc x mc reflective star coupler based onmcx1 tree coupler.
implementation. Further, SOAs are also better suited as post or preamplifier since these can
be integrated with either the transmitter or the receiver chips. Therefore, SOAs have been
considered in the studies reported in the following chapters.
36
Chapter 3
Semiconductor Optical Amplifier andCoding in OOK System
Fiber optic broadcast networks can support only a limited number of users because of
constraint on the transmitter power. It is desirable to have large number of users to utilize the
The work reported in this chapter has resulted in the following publications.
1. V. K. Jain, Y. N. Singh and H. M. Gupta, "Power Penalty due to Optical Amplifier InducedCrosstalk in Non-Coherent OOK Transmission Systems,"Journal of Optical Communications,Vol.16, No.5, Oct.1995, pp.194-196.
2. Y. N. Singh, V. K. Jain and H. M. Gupta, "Effect of Reed-Solomon Code on Laser LinewidthRequirements of BPSK Homodyne Optical Communication Systems,"Journal of OpticalCommunications,Vol.16, No.6, Dec.1995, pp.207-210.
3. Y. N. Singh, V. K. Jain and H. M. Gupta, "Reed Solomon Code and Semiconductor OpticalPreamplifier in OOK Communication System: A Comparative Study,"Journal of OpticalCommunications(accepted for publication).
4. Y. N. Singh, V. K. Jain and H. M. Gupta, "Effect of Error Correcting Codes on Laser LinewidthRequirements in Optical Binary Phase Shift Keying Communication Systems," Presented inIXth
National Convention of Electronics and Telecommunication Engineers,University of Roorkee,Roorkee, India, March 30-31, 1994.
5. V. K. Jain, Y. N. Singh and H. M. Gupta, "Effect of Optical Amplifier Induced Crosstalk in TwoChannel Non-Coherent OOK Transmission System," Presented inIXth National Convention ofElectronics and Telecommunication Engineers, University of Roorkee, Roorkee, India,March 30-31, 1994.
capacity of network. The number of users can be increased by increasing the power budget,
reducing the loss in the network, using electronic repeater and optical amplifiers. The power
budget can be improved by using coding techniques. The use of coding and semiconductor
optical amplifier (SOA) to increase the network size have been considered in this chapter. For
37
their comparative study, a point-to-point on-off keying (OOK) communication link has been
considered. The receiver structure considered is shown in Fig.3-1. It consists of a PIN
photodetector followed by a Gaussian filter with the frequency response
(3.1)
Here, f is the frequency andBe the electrical bandwidth of the filter. This filter is followed
by sampling, threshold and decision circuits.
Fig.3-1a The system block diagram for optical communication system with codingscheme.
Fig.3-1b The system block diagram for optical communication system with SOA aspreamplifier.
38
The electrical signal at the receiver output is corrupted by additive shot and thermal
noise of photodetector. Both types of noise are considered to be white Gaussian with power
spectral densities (psds) [30]
(3.2a)
and
(3.2b)
respectively. In the above equations,Ro is the responsivity of the photodetector,Pr the
received optical power level which becomesPr(1) for bit 1 andPr(0) for bit 0. These are
given by
(3.3a)
and
(3.3b)
whereε is the extinction ratio andPra (= [Pr(1) + Pr(0)]/2) the average received optical power
level. In the above equations,e is the electron charge,kb the Boltzmann’s constant,T the
temperature of receiver in Kelvin andRL the receiver load resistance.
39
The receiver performance in terms of required recieved optical power level has been
computed for (i) uncoded system, (ii) coded system with decoding and (iii) uncoded system
with optical preamplifier. The Gaussian filter in the receiving system is optimized for uncoded
transmission. The coding in the system increases the bit rate and hence intersymbol
interference (ISI). In order to evaluate the degradation due to ISI, performance of coded
system without decoding has been evaluated. Any coding gain should be measured with
respect to the above performance. Section 3.1 presents the analysis of uncoded system. In
section 3.2, coded system without decoding and with decoding has been considered. Uncoded
system with SOA has been analyzed in section 3.3. A comparative study of above systems
based on a practical example is given in section 3.4. Section 3.5 contains the observations and
conclusions of this study.
3.1 Uncoded System
The Gaussian filter in the receiver reduces noise by removing noise outside the
frequency band of interest. But it also causes ISI. Increase inBe results in decrease in ISI and
increase in noise after the filter and vice-versa. Hence, there exists an optimal filter
bandwidth.
Worst-case degradation due to ISI can be modelled by considering worst-case
waveforms for bit 1 and 0. These waveforms decide the eye opening. For bit 1 and 0, the
worst-case waveforms correspond to bit sequences ...0001000... and ...1110111... respectively.
The waveforms before and after the filter are shown in Fig.3-2. When the sampling is done
40
in the middle of bit, signal levelsS1 andS0 corresponding to worst-case sequences for bit 1
and 0 are given by
(3.4a)
and
(3.4b)
where
(3.5a)
and
(3.5b)
In the above equations,h(τ) is the impulse response of the Gaussian filter,Tb the bit duration.
The a1(τ) and a0(τ) are the worst-case waveforms for bit 1 and 0 respectively. The eye
opening will beS1-S0.
41
For an additive Gaussian noise with psdSN(f), variance after the Gaussian filter is
Fig.3-2 Worst-case waveform patterns for (a) bit 1 and (b) bit 0 before and after theGaussian filter.
given by
(3.6a)
If the noise is white i.e.SN(f)=SN. Using Eqn.3.1 in the above equation,σn2 is given by
42
(3.6b)
In an uncoded system,SN corresponding to bit 1 and 0 is given by sum ofSshot andSth. Noise
variancesσ2(1) andσ2(0) corresponding toS1 andS0 are determined from Eqn.3.6b. The bit
error rate (BER) which equalises the error rates forS1 andS0 is given by
(3.7)
The above analysis is quite general and the system performance can be evaluated for any bit
rateR (= 1/ Tb). The filter can be optimized to minimize the effect of ISI at a given bit rate.
When bit rate is increased (as in coding), the above optimization is not valid and the system
performance degrades due to increased ISI. The degradation in performance is evaluated using
the above general model (Eqns.3.4 to 3.7).
3.2 Coded System
Coding is introduced in the system by encoding the input signal to the transmitter and
decoding the receiver output signal (Fig.3-1a). As mentioned earlier, the bit rate increases in
the system due to coding. The increase depends on the amount of redundancy introduced by
coding scheme. When the data rate isR b/s and (N,k,t) block code is used, the coded bit rate
becomesR(N/k) b/s. Here,N is the number of symbols in the block,k the data symbols in the
block andt the number of symbols which can be corrected by the error correcting code. The
43
increased bit rate leads to more ISI as the receiver is same as in the uncoded system. It results
in increase in BER. Some errors are corrected in the decoding process leading to decrease in
BER. If the decrease in BER is more than the increase due to ISI, there will be a coding gain.
For a (N,k,t) block code, the symbol error rate after decodingPes(ad) is given by
[72, 99, 102]
(3.8a)
wherePes(bd) is the symbol error rate before decoding. It is related to bit error ratePe by
(3.8b)
In the above,n is the number of bits in a symbol. For example, in systematic Reed-Solomon
(R-S) (31,27,2) code, there are 31 five bit symbols, 27 data symbols and 4 parity symbols.
Therefore, in Eqn.3.8, values ofN, k, t andn are 31, 27, 2 and 5 respectively.
In the coded system, the bit rate becomes higher and the BER can be determined using
the same approach as in the uncoded system. This BER is used to determine the symbols
error rate before decodingPes(bd) from Eqn.3.8b. The R-S code will reducePes(bd). The reduced
symbol error rate after decodingPes(ad) can be determined using Eqn.3.8a. To compare the
44
performance of coded system with the uncoded system, BER for coded system is required to
be known. This can be determined from Eqn.3.8b by replacingPes(bd) with Pes(ad) and then
determiningPe using a suitable search technique. The BER also includes the errors in the
parity symbols which are discarded after decoding. Hence, the BER after discarding parity
symbols isPe(k/N). The system performance for R-S (31,27,2) code is evaluated using the
above approach and results are shown in Fig.3-3.
3.3 Uncoded System with Optical Amplifier
In this analysis, an SOA has been considered as preamplifier. It is modelled as
travelling wave amplifier (TWA). The SOA alongwith the amplified signal also produces ASE
noise which beats with signal and itself at the photodetector. The psd of various noise
components at the photodetector is shown in Fig.2-1.
There is a dc component due to ASE-ASE beat noise which gives rise to shot noise
with psd
(3.9)
The above is modelled as white Gaussian noise [63]. It adds to shot noise produced by the
signal. In Eqn.3.9,Ssp is the ASE noise psd andBo the bandwidth of optical filter. TheSsp is
given by
45
(3.10)
wherensp is the spontaneous emission factor,G the gain of OA,h the Planck’s constant and
ν the optical frequency.
The noise variance at the filter output due to ASE beat noise components is
determined by using Eqn.3.6a and noise psds are shown in Fig.2-1. These are given by
(i) ASE-ASE beat noise
(3.11a)
(ii) ASE-signal beat noise
(3.11b)
46
(iii) ASE shot noise
(3.11c)
In the above,Pin is the optical power at the input of optical preamplifier. The total noise
variance at filter output is given by
(3.12)
In order to compute the BER, received power levels for bit 1 and 0 are determined for
a given average received power level and extinction ratio from Eqn.3.3. Corresponding
amplifier gainG(1) andG(0) for bit 1 and 0 respectively are determined using these received
power levels and the amplifier gain saturation formula given in Eqn.2.4 [30]. The optical
power levels falling on photodetector for bit 1 and 0 arePin(1)G(1) and Pin(0)G(0)
respectively. Here,Pin(1) andPin(0) are input optical power levels to SOA for bit 1 and 0
respectively. The signal current after the Gaussian filter is determined for bit 1 and 0
following the same approach as in section 3.1. There is an optical bandpass filter of
bandwidthBo between SOA and photodetector (refer to Fig.3-1b). It is used to limit the ASE
noise. The noise variances for bit 1 and 0 are determined from Eqns.3.11 and 3.12 using the
ASE noise psd, optical signal power levels for bit 1 and 0 and optical filter bandwidthBo.
These are used to determine BER from Eqn.3.7.
47
3.4 Example
The results for a sample system are computed and analyzed in this section. Following
are the system parameters:
Bit rate (uncoded system),R 1 Gb/s
Optimum BW of Gaussian filter,Be 1.5 GHz
Operating wavelength,λ 1.55 µm
Quantum efficiency of photodetector,η 0.95
Coding scheme R-S (31,27,2)
Bit rate after coding 1.14 (=32/27) Gb/s
Unsaturated gain of SOA,G0 29 dB
Saturation power level,Psat 10 dBm
BW of optical filter, Bo 10 GHz
Extinction ratio,ε 0
The BER is determined as a function of average received signal power level for (i) uncoded
system, (ii) coded system without decoding, (iii) coded system with decoding and (iv)
uncoded system with optical preamplifier. Variations of log10(BER) with received signal
power levelPra (in dBm) are shown in Fig.3-3.
It is seen from the above figure that a coded system without decoding performs worse
than the uncoded system. This is expected as coding increases bit rate which in turn increases
the ISI and therefore the performance becomes worse. Once the received signal is decoded,
the performance improves because of error corrections. R-S(31,27,2) code for a BER of 10-9
48
provides coding gain of 1.7 dB. When optical preamplifier is used instead of coding,
Fig.3-3 Variations of BER vs received power level (dBm) for (i) uncoded system, (ii)coded system without decoding, (iii) coded system with decoding and (iv)uncoded system with SOA as preamplifier.
improvement in receiver sensitivity is about 21.2 dB. It implies that use of optical amplifier
improves the system performance much more than the use of coding.
3.5 Conclusions
It is concluded that in an OOK communication system, use of SOA is advantageous
as it provides more improvement ( > 20 dB) as compared to coding. Although the above
conclusion is based on R-S code, it will remain valid for all other codes too. The level of
49
improvement depends upon the received optical power level and coding scheme used. Use of
coding cannot provide coding gains in the vicinity of 20 dB.
Another advantage of SOA over coding is that it can amplify signals at high bit rates
(> 1 Gb/s). The practical implementation of encoder and decoder at such a high bit rate is
difficult. Further, a single SOA can handle multiple WDM channels. Therefore, in chapters 4
and 5 of the thesis only the use of SOAs in network has been considered.
50
Chapter 4
Semiconductor Optical Amplifiers inWDM Star Topology
In a star topology network, the transmitted signal from all the users are combined
The work reported in this chapter has appeared in the following publications.
1. Y. N. Singh, V. K. Jain and H. M. Gupta, "Semiconductor Optical Amplifiers in WDM StarNetworks,"IEE-Proceedings Optoelectronics,Vol.143, No.2, April 1996, pp.144-152.
2. Y. N. Singh, V. K. Jain and H. M. Gupta, "On Placement of Semiconductor Laser Amplifiers inWDM Star Networks,"Proc. National Conference on Optical Communications, J.K.Institute ofApplied Physics & Technology, University of Allahabad, Allahabad, India, Feb.22-24, 1995,pp.66-78.
in a star coupler and then distributed to all the receivers. The star coupler can be
centralized or distributed. Generally, the star coupler distribute the transmitted signal power
equally among the users. Consequently, star topology supports maximum number of users
as compared to other passive broadcast topologies viz. bus, ring and tree.
The semiconductor optical amplifiers (SOAs) can be placed in the star network to
amplify the optical signal. These will increase the supportable number of users. The SOAs
can be placed in a star either after the transmitters as postamplifiers or before the receivers
as preamplifiers. In case of WDM star networks, postamplifiers amplify single channel
signal only, while preamplifiers amplify signals in multiple channels. In the latter case,
there may be interchannel crosstalk.
51
In this chapter, the above SOA placement schemes are analyzed. Section 4.1 presents
the description of the star network. Section 4.2 discusses the reflection due to amplifier.
Noise variances due to ASE and signal beat noises are determined when the receiver uses
an ideal filter. In section 4.3, approach used in analyses is described. The analyses of star
without SOA, with postamplifier and preamplifier are presented in sections 4.4, 4.5 and 4.6
respectively. In section 4.7, an example with practical system parameters has been
considered. Finally, conclusions are given in section 4.8.
4.1 System Description
In a NuxNu star network, every user is provided with a transmitter and receiver pair.
In the simplest arrangement [32, 61], each user is assigned a dedicated transmit wavelength
in the 1.5 µm waveband. The modulation scheme considered is the binary intensity
modulation. When extinction ratioε is zero, it becomes an on-off keying system. The
transmitted signal power is equally distributed to all the receivers by the star coupler. Each
user receives the signals on all the wavelengths. One of the wavelengths is selected using
an optical filter and then detected using a photodetector. The above mentioned star coupler
is made of 3 dB 2x2 couplers. An 8x8 star coupler consisting of 2x2 couplers is shown in
Fig.4-1. In general, aNuxNu star coupler has log2Nu stages and requires (Nu/2)log2Nu number
of 3 dB 2x2 couplers. The total insertion lossLti of a NuxNu star coupler is given by
(4.1)
52
whereLi is the insertion loss of an individual 3 dB 2x2 coupler. The power split due to star
coupler may not be uniform due to practical limitations. This nonuniformity has been
considered in the analysis in terms of coupler variability,Lcv, which is the worst-case
reduction of power in the output port. Each user is connected to star coupler using a single-
mode dispersion flattened fiber. Consequently, the input and output ports ofNuxNu coupler
are spliced to optical fiber. Each of these splices introduces a loss ofLsp dB.
Fig.4-1 An 8x8 star coupler consisting of 3 dB 2x2 couplers.
At receivers, ideal optical filters are used. Therefore, there is no interchannel
crosstalk due to these filters. These filters introduce a insertion loss ofLfi dB. The filters
can be tunable or fixed wavelength type depending on the media access control (MAC)
protocol. When receiver arrays are used to receive more than one channel at a time,
demultiplexers can be employed instead of filters. Optical filters are followed by PIN
photodetectors in each of the receivers to detect the optical signal.
53
The use of SOAs is expected to increase the number of users or decrease the
required transmitter power in the star network. However, the presence of amplifier noise
and gain saturation effect is expected to partially reduce the above advantages. When SOAs
amplify multiple channels, total optical power at the SOA input varies randomly since light
is independently modulated in each channel. This results in interchannel crosstalk. The
signal power at the amplifier output in a channel varies according to the gain fluctuations
induced by modulation in other channels even when the input power in the channel is
constant. This is the crosstalk induced by gain saturation in the amplifier and is often
referred as cross-saturation. The cross-saturation effect increases with the increase in the
number of wavelength channels. Therefore, it is more severe when larger number of
wavelengths are used in the system. In the above system, maximum cross-saturation occurs
as Nu wavelengths are used. Hence this will provide upper bound on the degradation due
to cross-saturation for the WDM star network.
4.2 Amplifier Model
The gain of SOAs reduces with the increase in input power level. This reduction
arises due to gain saturation. The saturated gain of SOAs is given by Eqn.2.4. The
amplified spontaneous emission (ASE) noise is also present in the amplifier output
alongwith the amplified signal. The psd of ASE noise is given by Eqn.2.5. At the
photodetector, ASE noise beats with itself, signal and echo signal if present. The psds of
ASE-ASE and ASE-signal beat noise components are shown in Fig.2-1. The noise variances
of the various noise components, assuming an ideal electrical filter of bandwidthBe in the
receiver, are given by
54
(i) ASE-ASE beat noise [63, 90]
(4.2a)
(ii) ASE-signal beat noise [63, 90]
(4.2b)
When an echo signal is present, ASE-echo beat noise variance is given by Eqn.4.2b by
replacing Pr by the echo powerPecho. ASE-ASE beating also produces a dc component
resulting in shot noise. The variance of this shot noise is given by
(4.3)
In addition to signal amplification, the amplifiers also reflect signals. The reflection
coefficient of the amplifier is given by (Appendix-I).
(4.4)
In the above,R1 and R2 are the facet reflectivities andG the single pass gain of SOA.
55
4.3 Evaluation of Minimum Required Transmitter Power
Once the relationship between bit error rate (BER) and transmitter power,Pta, is
known for a given number of users,Nu, minimum requiredPta can be determined using this
relationship. Therefore, models to determine BER as a function ofPta andNu are formulated
in the following sections. These models are used to evaluate the performance of star
network without amplifier, with postamplifier and with preamplifier. In the analysis,
reflection noise due to filters and coupler have been neglected. Optical filters are assumed
to be ideal so that these do not introduce any crosstalk. Further, responsivity of
photodetectors is assumed to be independent of wavelength. The effect of finite extinction
ratio of transmitted pulse has been considered in the analysis.
4.4 Star without Amplifier
The WDM star topology is shown in Fig.4-2. Each transmitter is assigned an unique
operating wavelength and the coupler distributes signals of all wavelengths to all the
receivers. The power received at the photodetector for bitbc (bc is either 1 or 0) is
given by
(4.5)
where
56
(4.6a)
(4.6b)
In the above equations,Pta represents the average transmitter power andε the extinction
ratio. The lossLtr between transmitter and receiver excluding the split loss of star coupler
is given by
(4.7a)
or equivalently
(4.7b)
The above does not include the split loss of star coupler which has been included by the
factor 1/Nu in Eqn.4.5. In the above equation,α is the attenuation coefficient of fiber in
dB/km, L the length of fiber from user to star coupler in km,Lfi the filter insertion loss,
Lcv the loss due to nonuniformity in the power splitting by the star coupler andLsp the
splice loss in dB.
57
The signal current and noise variance for bitbc (bc = 0 or 1) at photodetector output
Fig.4-2 Star network without optical amplifier.
are given by
(4.8a)
and
(4.8b)
wherekb is the Boltzmann’s constant,T the temperature in Kelvin,R0 the responsivity and
RL the load resistance of the photodetector. The first term on right hand side of Eqn.4.8b
represents the shot noise and second term the thermal noise. The average probability of
error with the threshold level which equalises the BER for bit 1 and 0 is given by
58
(4.9)
It is obvious thatPe is determined fromIsig(1) and Isig(0), σ(1) andσ(0) which in turn are
determined fromPr(bc) and hence fromPt(bc). The Pt(bc) is determined fromPta. ThusPta
determinesPe. Alternatively, for a givenPe, Pta can be computed by a suitable search
technique.
4.5 Star with Postamplifier
In order to reduce the requiredPta, SOAs can be used in the star topology. In this
section, SOAs are placed immediately after the transmitters (postamplifiers). The
performance of star network with unsaturated postamplifiers has been analyzed in this
section. Subsequently, the effects of amplifier gain saturation and reflection have been
included in the analysis.
4.5.1 Unsaturated Amplifiers
As the gain of unsaturated postamplifier isG0, the received signal powerPr(bc) is
given by
59
Fig.4-3 Star network with postamplifiers (A, B, ...F is echo path).
(4.10)
whereLta is the loss between transmitter and amplifier andLar the loss between amplifier
and receiver. These are given by
(4.11a)
and
(4.11b)
In Eqn.4.11b,Lcp is the coupling loss of an amplifier facet. The psd of ASE noise at the
receiver will be
60
(4.12)
This psd is not reduced by the factor 1/Nu due to the following reason. LetSspi be noise psd
at the receiver due toi th amplifier. It is given by
(4.13)
The total noise psd at the receiver should be sum of all the psds due toNu amplifiers.
HenceSsp will be
(4.14)
This is same as given in Eqn.4.12.
The signal current and noise variance for bitbc using Eqns.4.2 and 4.3 are given by
(4.15a)
and
61
(4.15b)
The first term in Eqn.4.15b corresponds to shot noise due to signal and ASE, second term
to ASE-signal beat noise, third term to ASE-ASE beat noise and fourth term to thermal
noise. The signal currentsIsig(bc) and noise varianceσ2(bc) from Eqn.4.15 are used in
Eqn.4.9 to determine average probability of errorPe.
4.5.2 Effect of Gain Saturation
In general, gain of SOAs is not constant and it is input powerPin dependent. The
gain reduces with the increase inPin. This will degrade the receiver performance which has
been investigated below. Let the amplifier gain corresponding to bit 1 and 0 beG(1) and
G(0) respectively. Therefore, the received signal power level for bitbc will be
(4.16)
The received ASE noise psd is different for bit 1 and 0. When the desired channel
has bit 1, one half of the remaining (Nu-1) channels are expected to have bit 0 and the
other half bit 1. The ASE noise from each amplifier gets distributed equally among the
62
outputs. Therefore, ASE noise psd from each amplifier will get reduced by a factor of 1/Nu
at the receiver input. The total ASE noise psd at the receiver for bitbc is
(4.17)
The first term in the above equation corresponds to the desired channel, second term to
channels having bit 0 and the third term to channels having bit 1.
The signal current and noise variance for bitbc are given by
(4.18a)
and
(4.18b)
The first term in Eqn.4.18b correspond to shot noise due to signal and ASE, second term
to ASE-signal beat noise, third term to ASE-ASE beat noise and last term to thermal noise.
The averagePe in this case can be determined using Eqn.4.18 alongwith Eqn.4.9.
63
4.5.3 Effect of Reflection Noise
Splices in the network produce back reflections resulting in echoes at the receivers.
A signal which has undergone 2i reflections will generatei-pass echo. Generally, the
reflection coefficient of splices is below -20 dB, therefore the echoes with two and more
passes can be neglected. When the delays suffered by echoes are greater than the coherence
time of optical signal, coherence between signal and echoes need not be considered. In the
network under consideration, distance between the reflection points is much greater than
coherence length. Hence, incoherent addition of signal and echo power has been considered.
In the network shown in Fig.4-3, reflection can occur at amplifier or at splice 1 or
at splice 2. Consequently, there would be three possible echo signals. Out of these, the echo
signals due to SOA and splice 1 will be strongest. This is so because loss between splice 1
and splice 2, and SOA and splice 2 (insertion loss of star coupler + splice loss + fiber loss)
is much higher than loss between SOA and splice 1. Hence, echo signal arising due to
splice 2 can be neglected.
Worst-case occurs when the signal bit and echo signal bit arrive synchronously at
the receiver. This gives upper bound on degradation due to echo. The probability of error
in this worst-case is obtained as follows.
Let the echo signal of bitbr interfere with the signal corresponding to bitbc. The
echo signal power at various points in the echo path A, B, ..., F (Fig.4-3) are given by
64
(4.19a)
(4.19b)
(4.19c)(4.19c)
(4.19d)
(4.19e)
(4.19f)
The received echo power,Pecho, is same as echo power at point F (Eqn.4.19f). In the above
equation,Las1 is the fiber loss between amplifier and splice 1,Rsp the splice reflection
coefficient. The parameterGp(br) represents the gain of amplifier when signal corresponding
to bit br passed through the amplifier. It is obtained by replacingPin with Pin(br, brr) in
Eqn.2.4. ThePin(br, brr) is given by
65
(4.20)
where Rf is the facet reflectivity of amplifier (Rf=R1=R2). In the above equation, it is
presumed that echo of bitbrr interfered with the signal corresponding to bitbr. The
parameterG′p is the gain when signal corresponding to bitbrr was amplified. In the worst-
case situation, it is assumed that no echo was present when signal corresponding tobrr was
amplified. Further,brr is assumed to be zero for maximum echo signal. In the above
equation, signal corresponding tobr and echo ofbrr are added together and used asPin in
Eqn.2.4. As such, the two optical signal powers cannot be added as these are entering the
amplifier from opposite ends. But the above addition corresponds to the worst-case scenario.
The amplifier gain G for the signal corresponding to bitbc under the same
assumption is given by
(4.21a)
where
(4.21b)
66
It is seen from Eqn.4.4 and the above equation thatRamp is function of G which in turn
depends uponbc and br.
The received signal power at the photodetector input will be
(4.22a)
The ASE noise psd at the photodetector is given by
(4.22b)
In the above equation, first term corresponds to bitbc in the desired channel, second term
to bit br in the desired channel, third term to signals from the remainingNu-1 amplifiers
and last term to echo signals from the remainingNu-1 amplifiers. Further, bitsbci, bri and
brri are bits in thei th channel corresponding to the bitsbc, br and brr respectively in the
desired channel. In the worst-case situation, bitsbrr and brri can be taken as 0. Thebci and
67
bri can be either 1 or 0 with equal probability. WhenPr, Pecho andSsp are known, the signal
current and noise variance are given by
(4.23a)
and
(4.23b)
In the Eqn.4.23b, additional fourth term represents the signal-echo beat noise.
It is evident from Eqn.4.23a that there are two signal levels corresponding to bit 1
as well as bit 0 depending on bitbr. The threshold is obtained using the highest level
corresponding to bit 0, the lowest level corresponding to bit 1 and the corresponding noise
variances. The threshold which equalizes the BERs for these levels is given by
(4.24)
With this threshold, the probabilities of error for bit 1 and 0 are given by
68
(4.25a)
and
(4.25b)
For equiprobable bit 1 and 0, average probability of error is given by
(4.25c)
4.6 Star with Preamplifier
In this scheme, all the wavelengths are amplified by each preamplifier and one of
these is selected by the filter. As in the postamplifier scheme, performance of star network
with ideal preamplifiers has been analyzed first. This analysis is extended to include the
effect of amplifier gain saturation and reflection noise.
69
4.6.1 Unsaturated Amplifier
The received power for bitbc is given by
(4.26)
where
(4.27)
is the loss between transmitter and amplifier without the split loss of coupler. TheLar
represents the loss between amplifier and receiver which consists of only the insertion loss
of filter, Lfi, and amplifier coupling loss,Lcp.
The ASE noise psd,Ssp, at the photodetector is determined from Eqn.4.12. It will
be same for bit 1 and bit 0. SubstitutingPr(bc) and Ssp in Eqn.4.15, the signal currents
(Isig(1) and Isig(0)) and noise variances (σ2(1) and σ2(0)) for bit 1 and 0 are obtained and
averagePe is computed using Eqn.4.9.
4.6.2 Effect of Gain Saturation
The cross-saturation leads to decrease in the average gain because of increase in the
number of channels and gain fluctuations due to randomness in the number of channels
70
having bit 1. This degrades the performance [46, 75, 76]. In this section, degradation due
to average gain reduction and gain fluctuations has been analyzed.
(i) Average Gain Reduction
The input power to the amplifier corresponding to bitbc is
(4.28)
Let N1 channels out of totalNu channels are having bit 1. Therefore, the total input power
to the amplifier is N1Pin(1) + (Nu-N1)Pin(0). The corresponding saturated gain of the
amplifier is given by
(4.29)
In order to determine the average gain, probability distribution of number of channels
having bit 1 is considered to be binomial. The probability ofN1 channels having bit 1 will
be
(4.30)
Therefore, the average gain is given by
71
(4.31)
The signal power received for bitbc will be
(4.32)
As Gav is independent of signal bit, the ASE noise psd for both bit 1 and 0 will be same.
It is given by
(4.33)
Eqns.4.32 and 4.33 are used to determine signal currents (Isig(1) and Isig(0)) and noise
variances (σ2(1) and σ2(0)) in conjunction with Eqn.4.15. ThenPe is computed using
Eqn.4.9.
(ii) Gain Fluctuations
Let N1 channels out ofNu-1 interfering channels are having bit 1. The corresponding
total amplifier input power for the bit bc in the desired channels is
Pin(bc) + N1Pin(1) + (Nu-1-N1)Pin(0). Therefore, the saturated gain of the amplifier will be
72
(4.34)
The probability thatN1 channels out ofNu-1 channels are having bit 1 is given by
(4.35)
For bit bc, the signal power and ASE noise psd at the photodetector is given by
(4.36a)
and
(4.36b)
The above equation is used to determine the signal current and noise variance corresponding
to bit bc. These are given by
(4.37a)
and
73
(4.37b)
Both Isig(1) andIsig(0) will have Nu levels depending uponN1. The threshold corresponding
to highest level ofIsig(0) and lowest level ofIsig(1) will be
(4.38)
The probability of error under the condition thatN1 interfering channels are having bit 1
is given by
(4.39a)
The averagePe will be
(4.39b)
74
4.6.3 Effect of Reflection Noise
In order to analyze the effect of reflection noise, the echo path A, B, ..., G as shown
in Fig.4-4 has been considered. Reflection between SOA and splice 2 has only been
considered because the loss between splice 1 and splice 2 and splice 1 and SOA is much
higher. The amplifier is saturated by the signal and echo signal power in the desired
channel and also the signal and echo signal power in the interfering channels. Let the echo
of bit br affect the signal corresponding to bitbc. Further, let theM1 interfering channels,
with probability P′M1, were having bit 1 when the signal corresponding tobr was reflected
by SOA to form the echo signal. The average echo signal power at the amplifier input in
the desired channel is given by
(4.40)
The average echo signal power in the remaining interfering channels will be
(4.41)
The P′M1 is obtained from Eqn.4.35 by replacingN1 by M1. The Ls2a represents the loss
between splice 2 and amplifier (fiber and amplifier coupling loss). TheRamp depends on the
gain G(br,M1) which is given by
75
(4.42a)
where
(4.42b)
Let N1 channels out ofNu-1 interfering channels have bit 1 when signal corresponding to
bit bc is amplified. The gain of amplifier for this signal is
(4.43a)
where
(4.43b)
In Eqn.4.43b, first term is the signal power in the desired channel, second term the echo
signal power in the desired channel, third term (in the square bracket) the signal power in
the interfering channels and last term the echo signal power in the interfering channels.
The signal power, echo signal power and ASE noise psd at the receiver are given
by
76
Fig.4-4 Star network with preamplifiers (A, B, ...G is echo path).
(4.44a)
(4.44b)
and
(4.44c)
The signal current and noise variance are determined using the above equations, which are
given by
(4.45a)
and
77
(4.45b)
As before there are many signal levels for both bit 1 and 0 and the threshold is computed
which equalizes the probability of error for the highest level for bit 0 and the lowest level
for bit 0. The probability of errorPe(br,N1) for a givenbr and N1 will be
(4.46)
The averagePe will be
(4.47)
whereP′N1 is given by Eqn.4.35.
78
4.7 Example
In this example, a star network withNu users (Nu=2, 4, 8, 16, ...) has been
considered. Data rate for each channel has been assumed to be 1 Gb/s. Typical values of
different parameters in the network are as follows [19, 47, 62, 87].
Quantum efficiency of photodetector,η 0.95
Length of fiber from user to star coupler,L 1 km
Attenuation coefficient of fiber,α 0.2 dB/km
Unsaturated amplifier gain,G0 29 dB
Saturation power level of amplifier,Psat 10 dBm
Optical filter bandwidth,Bo 10 GHz
Insertion loss of each 2x2 coupler,Li 0.5 dB
Insertion loss of splice,Lsp 0.5 dB
Output power variability ofNuxNu coupler,Lcv 0.5 dB
Amplifier facet reflectivities,Rf 10-5 (-50 dB)
Amplifier coupling loss,Lcp 3 dB
Receiver temperature,T 3000 K
Load resistance,RL 100 Ohms
Spontaneous emission factor,nsp 3.0
Electrical bandwidth of receiver,Be 1 GHz
Operating wavelength,λ 1.55 µm
Filter insertion loss,Lfi 0.5 dB
79
For this network, numerical computations have been made for various values ofNu
and a specified BER of 10-9. The required transmitter power is determined (i) without SOA,
(ii) with optical postamplifier and (iii) optical preamplifier. The above is computed for
different values of extinction ratio i.e.ε =0.0, 0.05, 0.10 and 0.15. Numerical computations
are also made to include the effect of gain saturation and reflection noise. These results are
shown in Figs.4-5 to 4-14. In the following, results and inferences based on the above
figures are discussed.
Fig.4-5 Variations of minimum required average transmitter powerPta with number ofusersNu for ε = 0.0 in postamplifier scheme
i. Use of an ideal amplifier reduces the required minimum transmitter power level in
both postamplifier and preamplifier schemes. The reduction is more in the postamplifier
80
than in the preamplifier because ASE noise undergoes higher attenuation in the former
Fig.4-6 Variations of minimum required average transmitter powerPta with number ofusersNu for ε = 0.05 in postamplifier scheme
scheme.
ii. Gain saturation in the amplifier results in an increase in the required transmitter
power Pta. The difference in power level is referred to as power penalty. In the
postamplifier scheme, the penalty becomes more severe with increasingNu. It can be
explained as follows. AsNu increases, split loss of the star coupler also increases.
Therefore, more transmitter power is required to compensate for this loss. It results in
decrease in gain of the amplifier owing to an increase in gain saturation. The penalty
becomes so severe afterNu=512 that it overcomes the amplifier gain resulting in
degradation of system performance. The reason for gain saturation penalty exceeding
81
unsaturated amplifier gain is that for largeNu, gain for bit 1 is almost unity due to
Fig.4-7 Variations of minimum required average transmitter powerPta with number ofusersNu for ε = 0.10 in postamplifier scheme
saturation effect and hence ASE noise psd is negligible. However for bit 0, gain is much
more than unity and this results in substantial ASE noise psd. Therefore, on an average the
noise level is more than the noise level without amplifier. It degrades the system
performance for largeNu. The same trend is observed for all values of extinction ratio,ε.
The gain saturation effect increases with the increase inε.
In the preamplifier scheme, the effect of average gain saturation is small for low
values ofNu. It increases with an increase inNu. It is observed that degradation due to gain
saturation effect is much less in this scheme than in the postamplifier scheme because of
much lower average power at the amplifier input.
82
The effect of gain fluctuations in the preamplifier first increases withNu and after
Fig.4-8 Variations of minimum required average transmitter powerPta with number ofusersNu for ε = 0.15 in postamplifier scheme
attaining a maximum value decreases with the increase inNu (Figs.4-9 to 4-12). Since the
effect of gain fluctuations depends on the variance of probability density function of gain
which increases withNu, for low value of Nu. However, for largeNu average gain shifts
towards the lower extreme of the range (1 toG0) and the levels are cluttered together. This
results in a decrease in variance withNu at largeNu. For some intermediate value ofNu,
the variance will be maximum. This explains the variations of effect of gain fluctuations
with Nu.
iii. The effect of reflection noise reduces with the increase inNu for both post and
preamplifier schemes. AsNu increases, split loss of the star coupler also increases which
83
results in increased required transmitter power. In the postamplifier scheme, it will give rise
Fig.4-9 Variations of minimum required average transmitter powerPta with number ofusersNu for ε = 0.0 in preamplifier scheme
to gain saturation and hence a reduction in amplifier gain, while in the preamplifier scheme,
the total power at the amplifier input increases with the increase in number of channels.
Therefore, amplifier gain reduces with an increase inNu in the preamplifier scheme also.
A reduction in amplifier gain means a decrease in amplifier reflectance which reduces the
degrading effect of reflection. It is also observed that preamplifier scheme is more severely
affected by reflection noise than the postamplifier scheme. This can be attributed to more
gain saturation in the postamplifier.
84
iv. Figs.4-13 and 4-14 show the variations of average required transmitter power,Pta,
Fig.4-10 Variations of minimum required average transmitter powerPta with number ofusersNu for ε = 0.05 in preamplifier scheme
with ε. It is observed thatPta increases with an increase inε as expected.
Figs.4-7 and 4-11 are used to present the data in tabular form in Tables 4-1 and 4-2.
The following observations are made from these tables.
v. With the use of unsaturated SOAs in the network, number of users is increased for
both the post and preamplifier schemes. Gain saturation and reflection noise reduce the
above advantages. For example, in the postamplifier scheme,Nu increases to 4096 from 64
for transmitter power level of 0 dBm. When gain saturation and reflection noise are
85
considered,Nu is 256. In general, the number of users will increase as the reflection
Fig.4-11 Variations of minimum required average transmitter powerPta with number ofusersNu for ε = 0.10 in preamplifier scheme
Table 4-1 Number of users supported in the postamplifier scheme forε=0.10.
Pta
(dBm)
Number of users
Without SOAs UnsaturatedSOAs
GainsaturatedSOAs
Gain saturatedSOAs withreflection (Rsp=-20dB)
0 64 4096 256 256
-10 8 512 128 64
-20 0 32 32 0
-30 0 4 4 0
86
coefficient of splice decreases for a fixed transmitter power level.
Fig.4-12 Variations of minimum required average transmitter powerPta with number ofusersNu for ε = 0.15 in preamplifier scheme
vi. In the preamplifier scheme, greater number of users are supported except whenPta
is very low andRsp is very high e.g.Pta = -10 dBm andRsp = -20 dB. It is observed that
the supportable number of users reduces with the decrease inPta and the increase inRsp.
However, networks are usually not designed for very low transmitter powers and reflection
coefficients due to splices is much lower than -20 dB.
vii. For a typical Pta of 0 dBm, the preamplifier scheme performs better than the
postamplifier scheme in terms of an increase in the number of users. When the transmitter
power level is low (less than -10 dBm) and reflection coefficient is high, the postamplifier
87
scheme is better. However, networks are not implemented for such low transmitter power
Fig.4-13 Variations ofPta with ε for different Nu in postamplifier scheme. Solid linescorrespond to gain saturated SOAs and dashed lines to gain saturated SOAswith reflection noise.
levels and high reflection coefficients.
4.8 Conclusions
In this chapter, placement of optical amplifiers in a WDM star network has been
investigated. The number of users supported by the star topology for post and preamplifier
schemes has been determined. The effect of gain saturation and reflection noise in both
these schemes has been evaluated in terms of number of users supported or the required
transmitter power level for a given BER. The analyses also consider the effect of extinction
88
ratio. When there is no gain saturation and reflection noise in the network, postamplifier
Fig.4-14 Variations ofPta with ε for different Nu in preamplifier scheme. Solid linescorrespond to gain saturated SOAs and dashed lines to gain saturated SOAswith reflections.
scheme performs better. In presence of gain saturation, postamplifier scheme performs better
for low transmitter power levels. However, such power levels are not used in practice.
When number of users and consequently transmitter power increases, performance in
postamplifier scheme degrades, while in the preamplifier scheme it improves. The power
penalty due to reflection noise reduces in both the schemes with the increase in the number
of users.
Overall, the preamplifier is a better scheme than the postamplifier in WDM star
topology networks. The formalism developed in this chapter has been used to evaluate the
89
performance of tree-net topology in chapter 5. A comparative study of star network and
Table 4-2 Number of users supported in the preamplifier scheme forε=0.10.
Pta
(dBm)
Number of users
WithoutSOAs
UnsaturatedSOAs
AveragegainsaturatedSOAs
AveragegainsaturatedSOAs withgainfluctuation
Average gainsaturated SOAswith gainfluctuationsand reflection(Rsp=-20 dB)
0 64 1024 1024 512 512
-10 8 128 128 128 0
-20 0 16 16 16 0
-30 0 2 2 2 0
tree-net has been made in the same chapter.
90
Chapter 5
Semiconductor Optical Amplifiers InWDM Tree-net
In past few years, tree-net topology has received the attention of network designers.
The work reported in this chapter has resulted in the following communications
1 Y. N. Singh, H. M. Gupta and V. K. Jain, "Semiconductor Optical Amplifiers in WDM Tree-net,"IEEE/OSA Journal of Lightwave Technology(under review).
It provides large geographical area coverage with less amount of fiber and easy
expandability. The protocols can be designed for these networks to achieve low latency and
bounded delay [57]. Such networks can be configured in broadcast mode using passive
components or active regenerators. However, use of passive components is preferred for the
reasons of reliability and lower cost. The capacity of these networks can be tremendously
increased by making use of wavelength division multiplexing (WDM). The tree-net is a two
level topology (Fig.5.1) consisting of star as main topology and folded bus as auxiliary
topology. In a purely passive tree-net, the number of users supported is limited by split and
distribution losses in star couplers. The number of users supported can be increased by
using semiconductor optical amplifiers (SOAs).
Like in a star network, several SOA placement schemes are also possible in a tree-
net. As shown in the previous chapter, preamplifier scheme (SOAs as frontend of receivers)
is a better arrangement in the star topology [100]. With this in view, placement of SOAs
91
after the root (Fig.5-1) has been considered in the tree-net. In this chapter, tree-net has been
analyzed with and without SOAs. The results have been computed in terms of increase in
the number of users or reduction in the required transmitter power level with the placement
of SOAs. Subsequently, a comparative study of tree-net and star network has been made.
Fig.5-1 Basic tree-net topology.
5.1 System Description
In a tree-net withb (= 2i, i is a natural number) branches andn number of users
per branch, total number of supported users areNu (= bn). A tree-net topology withb=4
and n=4 is shown in Fig.5-1 [57]. In this topology, the users termed ’1’ are first order
users, ’2’ are second order users and so on. Therefore, order of users varies from 1 ton.
92
The power loss in the above network can be reduced by realising the star portion as
multistage star coupler (Fig.5-2) [66].
Fig.5-2a Structure of star coupler in tree-net without amplifiers.
In the tree-net topology,Na (=2k, k=0, 1, 2, ...) number of SOAs can be used. There
are three cases for incorporating SOAs in tree-net viz. (i)Na is one (20), (ii) Na ia less than
b and (iii) Na is equal tob. These configurations are shown in Fig.5-3a, 5-3b and 5-3c
respectively for 4x4 star portion of a tree-net. In these configurations, 3 dB couplers are
used to make the star coupler of dimensionNaxNa (Na > 1). The amplifiers are attached at
the output of this star coupler. Further, the dimension of the above is increased by using
the 3 dB 2x2 couplers as combiners at inputs (A, B, ...) and splitters at outputs (A’, B’,
...). The 3 dB 2x2 couplers are also used to connect the users to the folded bus.
93
Fig.5-2b Structure of branches in a tree-net without amplifiers.
Fig.5-3a A 4x4 star coupler with one amplifier in tree-net.
In the following analysis, number of wavelength channels in the tree-net are assumed
to be b. In a simple media access control (MAC) protocol, users on each branch transmit
on an unique wavelength channel. The contention for transmission among the users on same
branch can be resolved using variety of single channel protocols such as random access
time out (RATO) [14], ALOHA etc.. Each user can receive simultaneously on all the
94
wavelengths using an array of receivers. In contrast to WDM star [100], more than one user
Fig.5-3b A 4x4 star coupler with two amplifiers in tree-net.
Fig.5-3c A 4x4 star coupler with four amplifiers in tree-net.
can share a wavelength channel in tree-net. This reduces the required size of receiver arrays
at all the receivers. The available bandwidth in a wavelength channel is shared among the
users in a branch. Like in star network, the acknowledgement of packets is not required in
the tree-net also as the transmitting users listen to their own packet. If the transmitted
packet is received back correctly, it is expected that the packet has also been successfully
transmitted to its destination. It is also assumed that each transmitter in the tree-net adjusts
its transmitter power such that the power received from its own transmitter is same as that
95
received from highest order user (4th order user in Fig.5-2b). Thus a farthest (highest order)
user from the root on the bus transmits maximum power. This implies that the optical
power level at the amplifier input in each channel is same.
5.2 Analytical Model
In order to analyze the effectiveness of SOAs in tree-net, following four cases are
considered i.e. tree-net (i) without SOAs, (ii) with unsaturated SOAs, (iii) with SOAs
having average gain saturation and (iv) with SOAs having average gain saturation and gain
fluctuations. The optical amplifier model used in the analysis is same as used in previous
chapters.
For the worst-case analysis, the highest order transmitter has been considered. It is
remarked that the choice of receiver for worst-case analysis is not obvious. This is because
signal as well as the ASE noise is minimum at the highest order receiver. For the lowest
order receiver, both the signal as well as the ASE noise are at the maximum. Therefore,
BER for different receivers is computed and the receiver giving maximum BER or worst-
case receiver is identified. The computed results show that highest order receiver always
gives the worst performance. The BER for all the cases mentioned above are computed
following the same approach as in chapter 4 [100]. In the tree-net without SOAs, receiver
of highest order has been considered for the worst-case analysis as the received signal is
minimum for it. The lossLtr between transmitter and receiver depends upon number of
users, number of branches, attenuation in fiber, splice and insertion losses. It is given by
96
whereXtr is the above loss in dB and is given by
(5.1a)
(5.1b)
Here,Lss is the fiber loss between two consecutive users on a bus,Li the insertion loss of
a 3 dB 2x2 coupler,α the attenuation coefficient of fiber in dB/km,L the length of fiber
between order one user and star portion of the network in km,Lsp the splice loss andLfi
the insertion loss of wavelength demultiplexer. The received optical power is determined
using the given transmitter power level and lossLtr. The noise variances at the receiver
(sum of shot noise and thermal noise) are determined for received optical power levels for
bit 1 and 0. The BER which equalizes the probability of error for bit 1 and 0 is computed
using the signal currents and noise variances.
When SOAs without gain saturation are used in the tree-net, the optical power level
in a channel at the amplifier input is determined using given transmitter power level and
loss between transmitter and amplifierLta. In addition to parameters which affectLtr, the
Lta also depends on number of SOAs. It is given by
97
(5.2a)
whereXta is the above loss in dB and is given by
(5.2b)
The received signal and ASE noise at the receiver of orderj (1 ≤ j ≤ n) are determined
using the unsaturated gainG0 of the amplifier and loss,Lar, between amplifier and the
receiver of orderj. The lossLar is given by
(5.3a)
where
98
(5.3b)
At the receiver of orderj, noise variance due to ASE-signal beat noise, ASE-ASE beat
noise, shot noise (due to signal and dc component of ASE-ASE beat noise) and thermal
noise are determined for bit 1 and 0. The BER which equalises the probability of error for
bit 1 and 0 is determined using corresponding signal levels and noise variances.
In presence of average gain saturation, signal power at the input of SOA is
determined as mentioned above. It is presumed that bits in all the channels at the input of
SOA are synchronised which produce maximum degradation [75, 76]. For a given number
of channels having bit 1, total input power to SOA is determined and used for finding the
saturated gain. The average gain is determined by averaging this gain over the binomial
distribution of number of channels having bit 1. The received optical signal and ASE noise
at the input of the receiver are determined using this average gain. These are used to obtain
the signal levels and noise variances at the receiver output which are used to determine the
BER.
99
In the last case i.e. tree-net with SOAs having average gain saturation and gain
fluctuations, the BER is determined for a given bit pattern in the interfering channels. It
is then averaged using the binomial distribution of interfering channels having bit 1 to
determine overall BER. For a given channel, the power level at the input of SOA is
determined as in case of tree-net with unsaturated SOAs. The saturated gain of SOA for
bit 1 and 0 in desired channel is determined for a given number of interfering channels
having bit 1. Then received optical signal power and ASE noise psd are determined at the
input of receiver of orderj. These are used to determine signal levels and noise variances
at the receiver output for bit 1 and 0 in the desired channel. As there are (b-1) interfering
channels,b signal levels for both bit 1 and 0 will exist depending upon number of
interfering channels having bit 1. The highest signal level for bit 0 is always less than the
lowest level for bit 1 [75]. Using these two levels, threshold is determined which equalises
the probability of error for these levels. The probability of error for each signal level is
determined using the corresponding noise variance and the computed threshold. This
probability of error is averaged presuming equiprobable bit 1 and 0 in the desired channel
and the binomial distribution of number of interfering channels.
5.3 Example
The effectiveness of optical amplifiers on a sample tree-net is studied using the
above model. The tree-net has the following parameters:
Maximum allowed transmitter power,Pta 0 dBm
Desired BER 10-9
100
Insertion loss in 2x2 coupler,Li 0.5 dB
Unsaturated gain of SOAs,G0 29 dB
Saturation power level in SOAs,Psat 10 dBm
Distance between the root and first order user on a branch,L 1 km
Distance between consecutive nodes on a branch,Lss 100 m
Attenuation coefficient of fiber,α 0.2 dB/km
Load resistance of receiver,RL 100 Ω
Operating wavelength,λ 1.55 µm
Optical BW of a passband in wavelength demultiplexer,Bo 10 GHz
Electrical bandwidth of receiver,Be 1 GHz
Temperature of receiver,T 300 oK
Spontaneous emission factor,nsp 3.0
Insertion loss of splice,Lsp 0.5 dB
Insertion loss of wavelength demultiplexer,Lfi 0.5 dB
Extinction ratio,ε 0.10
Numerical results for the sample tree-net are computed using the above parameter
values. Table 5.1 shows the number of users supported,Nu, and minimum required
transmitter power level,Pta, for various values ofn without SOAs. Variations ofNu with
Na for three cases viz. tree-net with (i) unsaturated SOAs, (ii) average gain saturated SOAs
and (iii) average gain saturated SOAs with gain fluctuations are shown in Figs.5-4, 5-5 and
5-6 respectively. The numbers shown in brackets are the minimum required transmitter
power levels (dBm) for the corresponding values ofNu and Na. For example, in Fig.5-4a
whenn=2 andNa=32, Pta is -5.4 dBm and correspondingNu is 512. It is remarked that plot
101
for n=1 (not shown here) is similar to the ones forn=2. It is observed that for a given
Fig.5-4a Variations ofNu with Na (unsaturated SOAs) forn=2. The values in thebrackets are corresponding requiredPta in dBm.
Fig.5-4b Variations ofNu with Na (unsaturated SOAs) forn=3. The values in thebrackets are corresponding requiredPta in dBm.
value ofn, increase inNa may result in increasedNu or reducedPT or both. Increase inNa
102
does not necessarily increaseNu. Since in tree-net,Nu varies in discrete steps, the next
Fig.5-5a Variations ofNu with Na (average gain saturated SOAs) forn=2. The valuesin the brackets are corresponding requiredPta in dBm.
Fig.5-5b Variations ofNu with Na (average gain saturated SOAs) forn=3. The valuesin the brackets are corresponding requiredPta in dBm.
103
higher value may not be supported if the requiredPta is above 0 dBm. For example,Nu is
Fig.5-6a Variations ofNu with Na (average gain saturated SOAs with gain fluctuations)for n=2. The values in the brackets are corresponding requiredPta in dBm.
Fig.5-6b Variations ofNu with Na (average gain saturated SOAs with gain fluctuations)for n=3. The values in the brackets are corresponding requiredPta in dBm.
104
192 for n=3 andNa=4 (Fig.5-4b). When theNa is increased to 8,Nu is still 192 because
for the next admissible numberNu=384, requiredPta is more than 0 dBm. But the next
higher value ofNa i.e. 16 results in increase ofNu to 384. It is noticed that increase inNa
from 4 to 8 results in reduction inPta from -2.6 dBm to -5.7 dBm and no change inNu.
Therefore,Na=8 is not useful as the availablePta is 0 dBm and there is no increase inNu.
Table 5.1 Number of users and requiredPta for the tree-net without SOAs.
Number of users perbranch,n
Tree-net without SOAs
Nu=bn Pta (dBm)
1
2
3
64
32
12
-2.2
-2.2
-1.8
When average gain saturated SOAs are considered, a decrease inNu is observed
compared to above. For example, whenn=2, Na=16 supports 512 users for unsaturated
SOAs and 256 users for average gain saturated SOAs. This behaviour is true for all values
of n. Further, the gain fluctuations in SOAs either increasePta or reducesNu. For example,
when n=2, Na=16 still supports same number of users as in average gain saturation case,
but Pta has increased to -2.6 dBm from -3.8 dBm showing a power penalty of 1.2 dB. An
example of reduction inNu is n=3, Na=8 whenNu reduces from 192 to 96 (see Figs.5-5b
and 5-6b).
105
In tree-net topology,n=3 provides the values ofNu which are not admissible in star
topology. This is advantageous in certain cases as seen in Table 5.2. The table shows the
values ofNu corresponding to eachNa for all the three cases. For each case, minimum
requiredPta has also been computed and shown. It is observed that maximum number of
users are supported byn=2 in most of the cases. The worst-case losses inn=1 and 2 are
almost same, but the number of wavelengths used inn=2 are halved. This results in reduced
effect of average gain saturation and fluctuations. In some cases,n=3 supports more number
of users thann=2 (e.g.Na=32 supports a maximum of 384 users forn=3 in average gain
saturation case). This is due to the peculiarity of number of users admissible in tree-net for
n=3.
A comparison of star network with tree-net is given in Table 5.3. It is observed
from this table that both the networks can support 64 users without SOAs. Both star
network and tree-net with SOAs can support 128 users. However, the former needs 128
SOAs and the latter 4 SOAs. Similarly, star network can support 256 and 512 users with
256 and 512 SOAs respectively, while the tree-net requires 16 and 64 SOAs to support the
same number of users respectively. It is also observed that 1024 users are supported by the
tree-net only. The above is possible as the amplifiers are integrated within the star coupler
and the amplifier coupling loss is negligible. Therefore, the tree-net requires lesser number
of SOAs for a given number of supportable users. Both star network and tree-net cannot
support more than 1024 users irrespective of number of SOAs used.
106
Table 5.2 Maximum number of users andPta for a given number of SOAs. Numbers inbrackets are the corresponding values ofn.
Number ofamplifiers,Na
Unsaturated SOAs Average gain saturatedSOAs
Average gain saturatedSOAs with gain fluctu-ations
Nu (n) Pta (dBm) Nu (n) Pta (dBm) Nu (n) Pta (dBm)
1
2
4
8
16
32
64
128
256
512
1024
2048
128 (2)
128 (2)
256 (2)
256 (2)
512 (2)
512 (2)
1024 (2)
1024 (2)
2048 (2)
2048 (2)
2048 (2)
2048 (1)
-3.0
-6.1
-2.6
-5.7
-2.2
-5.4
-1.8
-3.8
-0.3
-1.5
-1.8
-1.8
64 (2)
64 (2)
128 (2)
192 (3)
256 (2)
384 (3)
512 (2)
512 (2)
1024 (2)
1024 (2)
2048 (2)
2048 (1)
-3.4
-10.0
-3.8
-0.3
-3.8
-0.3
-3.4
-6.9
-2.2
-4.6
-0.3
-1.1
64 (2)
64 (2)
128 (2)
128 (2)
256 (2)
256 (2)
512 (2)
512 (2)
1024 (2)
1024 (2)
1024 (2)
-
-0.7
-8.9
-1.8
-8.9
-2.6
-8.5
-3.0
-6.5
-1.8
-3.4
-3.0
-
5.4 Conclusions
It has been observed that the gain saturation in SOAs affects the performance of
tree-net. It reduces number of users supported as compared to tree-net with unsaturated
SOAs. The gain fluctuations in SOAs further deteriorate the performance. Since the star
topology supports maximum number of users without SOAs, star network and tree-net are
107
compared. It is shown that the tree-net require lesser number of SOAs as compared to star
Table 5.3 Comparison of star network and tree-net in terms of number of SOAs requiredfor a given number of users.
Number of users,Nu Number of SOAs requiredStar Tree
64
128
256
512
1024
0
128
256
512
-
0
4
16
64
256
for a fixed number of supportable users. This is because of topological advantage of tree-
net in terms of wider choices of users per SOA. It is remarked that in comparison to star
network, tree-net offers distinct advantages in terms of more geographical coverage, less
usage of fiber and transmitter sharing between more than one user [83, 86].
108
Chapter 6
Conclusions
In the research work reported in this thesis, usage of semiconductor optical amplifiers
(SOAs) in wavelength division multiplexed (WDM) star network and tree-net has been
studied. The SOAs are used to alleviate the limitation on power budget and hence number of
users supported. Error correcting codes can also be used for this purpose. The use of SOA
and an error correcting code has been investigated in a point-to-point OOK link. It has been
observed that the improvement in power budget due to SOA exceeds the improvement due
to coding by approximately 20 dB. Therefore, the use of SOA is a much better option than
the use of an error correcting code. In view of this, only the SOAs are considered for the
placement in WDM star and tree networks.
Two SOA placement schemes (i.e. postamplifier and preamplifier) in WDM star
network have been investigated. The number of SOAs in these schemes are always equal to
number of users. Each user is assigned an unique wavelength for transmission. The study
shows that when unsaturated SOAs are used, the postamplifier scheme is better than the
preamplifier scheme. The reason for the above is that the amplified spontaneous emission
(ASE) noise is attenuated more in the postamplifier scheme than in the preamplifier scheme.
Consequently, the effect of ASE noise is less in the postamplifier scheme. When gain
saturated SOAs are considered, the supportable number of users is reduced in both the
postamplifier and the preamplifier schemes. The degradation increases with an increase in the
number of users in both the schemes. This is quite expected. However, the degrading effect
of gain saturation is relatively more in the postamplifier scheme. The SOAs in the
109
preamplifier scheme are affected by both average gain saturation and gain fluctuations. The
average gain saturation is dependent on number of WDM channels and hence number of
active users. The gain fluctuations depend on bit patterns in active channels. The analysis in
chapter 4 shows that the degrading effect of average gain saturation increases with an increase
in the number of users. However, the degradation due to gain fluctuations first increases to
a maximum value and then decreases. When reflection noise due to splices is also considered,
the performance of both the schemes degrades. The above degradation is more severe in the
preamplifier scheme than in the postamplifier scheme. The effect of nonzero extinction ratio
has also been studied. As expected, it has been observed that the degradation increases with
an increase in extinction ratio. In general, the preamplifier scheme performs better than the
postamplifier scheme and hence supports more number of users.
The tree-net topology is a more general topology of which star is a special case. The
tree-net can support 2in (i=1,2,...,n=1,2,...) users while star supports only 2i users. In the tree-
net, there exists the possibility of sharing transmitter sources using passive access node (PAN)
interface [86]. In this thesis, number of wavelengths in the tree-net is chosen to be equal to
number of branches. The SOAs are placed in the star coupler part of the tree-net. In contrast
to the star network, number of SOAs in the tree-net can be less than the number of branches.
The number of users supported by tree-net with unsaturated SOAs and saturated SOAs is
determined. As expected, the supported number of users reduces when SOAs are gain
saturated. When tree-net is compared with the star, it is observed that the tree-net can support
more number of users than star for a given maximum transmitter power level and number of
amplifiers. This advantage accrues due to the topology of the tree-net which provides wider
possible assignment of number of users for a given number of SOAs. In brief, it is concluded
110
that use of SOAs is a better choice to increase the supportable number of users in both star
network and tree-net. Further, the tree-net utilizes the SOAs more effectively as compared to
the star network.
In the work presented in this thesis, following assumptions and simplifications have
been made. The noise of the transmitting sources has not been considered. The dispersion in
fiber is neglected as distances involved are small for an appreciable dispersion. Modal noise
due to fiber [68] has been assumed to be absent. The couplers used are considered to be
wavelength independent. Further, the demultiplexers and filters are taken to be ideal.
Therefore, no crosstalk occurs due to these components. The responsivity of photodetectors
has been assumed to be wavelength independent over the range of operation.
In the foregoing analyses, SOAs are considered as travelling wave amplifiers (TWAs)
and the gain profile is assumed to be uniform in the operating wavelength range. Further, the
crosstalk in the SOAs are considered to arise only due to the gain saturation.
In this thesis, use of SOAs in only two of the many topologies i.e. WDM star and
WDM tree-net has been studied. Therefore, OA placement options can also be explored in
other broadcast topologies including multilevel topologies. It is remarked that multilevel
topologies may be advantageous in terms of number of OAs required for a given number of
users.
As mentioned in chapter 1, switched optical networks will be attractive in the future.
Therefore, the placement of OAs in these networks requires investigations. These switched
111
networks include wavelength routed networks in which wavelengths are directed to those parts
of the network where these are needed the most. The proper routing of wavelengths allows
wavelengths reuse in different parts of network [54].
In this thesis, SOAs have been considered because these can be easily integrated in
star coupler, transmitter or receiver. However, doped fiber amplifiers (DFAs) are finding
applications in wide area networks as in-line amplifiers. Therefore, analysis presented in this
thesis can be extended to the networks using DFAs.
Another important area where optical amplifier would be very useful is subscriber
access networks (SANs). In these, both WDM techniques and OAs can be used for connecting
large number of users to a central office. The topologies used in SANs have different
requirement as compared to LANs and WANs. The OA placement studies can be extended
to SANs considering these requirements.
In the above, use of OAs as signal amplifier for the purpose of increasing the size of
network has been suggested. The OAs can also function as switches and wavelength
convertors. Therefore, studies of optical networks which include these additional
functionalities of OAs are suggested.
It is concluded from the above that OAs will form an important part of the future high
capacity optical networks.
112
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Appendix - I
Derivation of Ramp(G)
Let the reflectivities of two facets of SOA beR1 andR2 as shown in Fig.A-1. TheEi
is the amplitude of the input electric field andEo1, Eo2, ...Eop are the output electric field
amplitudes after 0, 2, ...2(p-1) reflections. Here,p is an integer. LetEr1, Er2, ...Erp be the
reflected electric field amplitudes after 1, 3, ...(2p-1) reflections (see Fig.A-1). The amplitudes
of the output electric fields are given by
(A-1a)
(A-1b)
and
(A-1c)
whereβ is the propagation constant in the gain media,G the single pass gain in cavity and
Lg the length of gain media. The total output electric field is given by
(A-2)
123
In the above equation,p has been taken as infinity. Normally, it must be an integer part of
Fig.A-1 Reflected and transmitted signals in a Fabry-Perot amplifier.
Lc/(2xLg). TheLc is the coherence length of laser light and is related to laser linewidth as [7]
(A-3)
whereCf is the speed of light in the fiber and∆ν the laser linewidth. The coherence length
of laser output for a linewidth of 1 MHz andCf=2x108 m/s in glass fiber will be 63.64 m [7].
Therefore,m would be 31,820 assuming the OA cavity length to be 1 mm. Further, the
amplitude of the output field decreases at each reflection. It means higher order reflections
will have negligibly small contribution in the output electric field. Therefore, the
approximation of extendingm to infinity is valid. Equation A-2 can be written as
124
(A-4)
When the above series converges toG R1R2 <1,
(A-5)
Substitution ofEo1 from Eqn.A-1a gives
(A-6)
The transmittanceTamp is given by
(A-7)
It is seen from the above equation thatTamp will be maximum when 2βLg = 2πi wherei is an
integer. The maximum value ofTamp is referred asTmax and is given by
125
(A-8)
Like the transmitted electric fields, reflected electric fields are given by
(A-9a)
(A-9b)
or
(A-9c)
and
(A-9d)
Following the same approach as used in the evaluation of the total output electric field, the
total reflected electric field is given by
126
(A-10)
This equation is used to determine the reflectanceRamp of the amplifier. As mentioned earlier,
Tamp will be maximum when 2βL=2πi. Under the same condition, reflectance of the amplifier
Ramp is given by
(A-11)
127
128
Appendix -II
Statistics of Signal and Echo Beat Noise
In presence of reflection, the information signal and echo signal beat at the
photodetector to produce the signal-echo beat noise. The electric fields due to echo and the
information signals are given by
(B-1a)
and
(B-1b)
At the photodetector,eecho ander beat and produce the beat noise current
(B-2a)
where
(B-2b)
AssumingΘ to be uniformly distributed random variable between -π andπ, its pdf is given
by
129
(B-3)
Therefore, the mean and variance of beat noise current,iecho-sigare given by
(B-4a)
(B-4b)
130
Biography of Author
The author was born in Delhi in 1969. He obtained B.Tech. in Electrical Engineering
with honours from Regional Engineering College, Hamirpur, Himachal Pradesh in July 1991
and M.Tech. in Optoelectronics & Optical Communications from Indian Institute of
Technology, Delhi in December 1992. Since then he is pursuing his Ph.D in Electrical
Engineering Department, Indian Institute of Technology, Delhi. He is an associate member
of Institution of Electronics and Telecommunication Engineers (IETE), India. His academic
interests include Optical Computing, Optical Networks, Photonic Switching and Optical
Communications. He is also interested in MAC Protocols and Philosophy of Science.
131
132
List of Publications Resulted from the Thesis Research
A. Journals
1. V. K. Jain, Y. N. Singh and H. M. Gupta, "Power Penalty due to Optical AmplifierInduced Crosstalk in Non-Coherent OOK Transmission Systems,"Journal of OpticalCommunications, Vol.16, No.5, Oct.1995, pp.194-196.
2. Y. N. Singh, V. K. Jain and H. M. Gupta,"Effect of Reed-Solomon Code on LaserLinewidth Requirements of BPSK Homodyne Optical Communication Systems,"Journal of Optical Communications,Vol.16, No.6, Dec.1995, pp.207-210.
3. Y. N. Singh, V. K. Jain and H. M. Gupta, "Semiconductor Optical Amplifiers inWDM Star Networks,"IEE-Proceedings Optoelectronics,Vol.143, No.2, April 1996,pp.144-152.
4. Y. N. Singh, V. K. Jain and H. M. Gupta, "Reed-Solomon Code and SemiconductorOptical Preamplifier in OOK Communication System: A Comparative Study,"Journalof Optical Communications(accepted for publication).
5. Y. N. Singh, H. M. Gupta and V. K. Jain, "Semiconductor Optical Amplifiers inWDM Tree-net,"IEEE/OSA Journal of Lightwave Technology(under review).
B. Conferences
6. Y. N. Singh, V. K. Jain and H. M. Gupta, "Effect of Error Correcting Codes on LaserLinewidth Requirements in Optical Binary Phase Shift Keying CommunicationSystems," Presented inIXth National Convention of Electronics and TelecommunicationEngineers,University of Roorkee, Roorkee, India, March 30-31, 1994.
7. V. K. Jain, Y. N. Singh and H. M. Gupta, "Effect of Optical Amplifier InducedCrosstalk in Two Channel Non-Coherent OOK Transmission System," Presented inIXth National Convention of Electronics and Telecommunication Engineers, Universityof Roorkee, Roorkee, India, March 30-31, 1994.
8. Y. N. Singh, V. K. Jain and H. M. Gupta, "WDM Data Network," Presented inIXth
National Convention of Electronics and Telecommunication Engineers, University ofRoorkee, Roorkee, India, March 30-31, 1994.
9. Y. N. Singh, V. K. Jain and H. M. Gupta, "On Placement of Semiconductor LaserAmplifiers in WDM Star Networks," Proc. National Conference on OpticalCommunications, J.K.Institute of Applied Physics & Technology, University ofAllahabad, Allahabad, India, Feb.22-24, 1995, pp.66-78.
133