Solution 3
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Solution 3
7.41.
xp(t) =∞∑
n=−∞x(nTs)p(t− nTs)
= p(t) ⋆∞∑
n=−∞x(nTs)δ(t− nTs)
= p(t) ⋆ x(t)∞∑
n=−∞δ(t− nTs)
Thus
Xp(f) = P (f) · F
[x(t)
∞∑n=−∞
δ(t− nTs)
]
= P (f)X(f) ⋆ F
[ ∞∑n=−∞
δ(t− nTs)
]
= P (f)X(f) ⋆1
Ts
∞∑n=−∞
δ(f − n
Ts)
=1
TsP (f)
∞∑n=−∞
X(f − n
Ts).
2. In order to avoid aliasing, Fs = 1Ts
> 2W . Furthermore, the spectrum P (f)should be invertible for |f | < W .
3. X(f) can be recovered using the reconstruction filter∏( f2W ′ ) with W < W ′ <
1Ts
−W . In this case
X(f) = Xp(f)TsP−1(f)
∏(
f
2W ′ ).
7.181.
RX(t; τ) = E[x(t)x(t+ τ)]
= E[Y 2 cos(2πf0t+ θ) cos(2πf0(t+ τ) + θ)
]= E[Y 2]E [cos(2πf0t+ θ) cos(2πf0(t+ τ) + θ)]
=3
2cos(2πf0t)
SX(f) = F (RX(t; τ)) =3
4[δ(f − f0) + δ(f + f0)]
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2.
PX =
∫ ∞
−∞SX(f)df =
3
2.
SQNR =PX
E[e2]=
3× 4vPX
x2max
= 22v−1 ≥ 40dB = 104.
We have v ≥ 8, thus the required number of bits/sample and the bandwidthrequirement are 8 and 8f0, respectively.
3.
SQNR =PX
E[e2]=
3× 4vPX
x2max
dB= 10log10
PX
a2+ 6v + 4.8.
Thus, one extra bit increases the SQNR by 6dB. If the SQNR is to be increasedby 24dB, 4 more bits/sample must be introduced. The new minimum bandwidthrequirement is 12f0.
7.201.∫∞−∞ fX(x)dx = 1, then 3a = 1 which leads to a = 1
3 .
2.
PX = E[X2]
=
∫ 0
−2
x2(1
6x+
1
3)dx+
∫ 2
0
1
3x2dx
=10
9.
3. 2v = 32 leads to v = 5. Thus
SQNR = 10 log10PX
x2max
+ 6v + 4.8 = 10 log1010
9/4 + 30 + 4.8 ≈ 29.2dB.
4. BWreq = vW = 5× 12KHz = 60KHz.
5. ∆SQNR = 6∆v ≥ 20 leads to ∆vmin = 4.Then ∆BWreq = ∆vW = 4× 12KHz = 48KHz.
9.41. Taking the inverse Fourier transform of H(f), we obtain:
h(t) = F−1 [H(f)] = δ(t) +α
2δ(t− t0) +
α
2δ(t+ t0).
Hencey(t) = s(t) ⋆ h(t) = s(t) +
α
2s(t− t0) +
α
2s(t+ t0).
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2. If the signal s(t) is used to modulate the sequence In, then the transmitted signalis
u(t) =∞∑
n=−∞Ins(t− nT ).
The received signal is the convolution of u(t) with h(t). Hence,
y(t) = u(t) ⋆ h(t) =
( ∞∑n=−∞
Ins(t− nT )
)⋆(δ(t) +
α
2δ(t− t0) +
α
2δ(t+ t0)
)=
∞∑n=−∞
Ins(t− nT ) +α
2
∞∑n=−∞
Ins(t− t0 − nT ) +α
2
∞∑n=−∞
Ins(t+ t0 − nT )
Thus, the output of the matched filter s(−t) at the time instant t1 is:
w(t1) =
∞∑n=−∞
In
∫ ∞
−∞s(τ − nT )s(τ − t1)dτ
+α
2
∞∑n=−∞
In
∫ ∞
−∞s(τ − t0 − nT )s(τ − t1)dτ
+α
2
∞∑n=−∞
In
∫ ∞
−∞s(τ + t0 − nT )s(τ − t1)dτ
If we denote the signal s(t) ⋆ s(t) by x(t), then the output of the matched filterat t1 = kT is:
w(kT ) =∞∑
n=−∞Inx(kT − nT )
+α
2
∞∑n=−∞
Inx(kT − t0 − nT ) +α
2
∞∑n=−∞
Inx(kT + t0 − nT )
3. With t0 = T and k = n in the previous equation, we obtain:
wk = Ikx0 +∑n̸=k
Inxk−n
+α
2Ikx−1 +
α
2
∑n̸=k
Inxk−n−1 +α
2Ikx1 +
α
2
∑n̸=k
Inxk−n+1
= Ik
(x0 +
α
2x−1 +
α
2x1
)+∑n ̸=k
In
[xk−n +
α
2xk−n−1
α
2xk−n+1
].
The terms under the summation is ISI introduced by the channel. If the signals(t) is designed so as to satisfy the Nyquist criterion, then:
xk = 0, k ̸= 0
and the above expression simplified to
wk = Ik +α
2(Ik+1 + Ik−1) .
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9.5The pulse x(t) having the raising cosine spectrum given by (9.2.20/21) is:
x(t) = sinc(t/T )cos(πβt/T )
1− 4β2t2/T 2
The function sinc(t/T ) is 1 when t = 0 and 0 when t = nT . Therefore, the Nyquistcriterion will be satisfied as long as the function g(t) is:
g(t) =cos(πβt/T )
1− 4β2t2/T 2=
{1 t = 0bounded t ̸= 0
The function g(t) needs to be checked only for those values of t such that 4β2t2/T 2 =1 or βt = T
2 . However:
limβt→T
2
cos(πβt/T )
1− 4β2t2/T 2= lim
x→1
cos(π2x)
1− x2= lim
x→1− π
4xsin(
π
2x) = −π
4< ∞
Hence:
x(nT ) =
{1, n = 00, n ̸= 0
meaning that the pulse x(t) satisfied the Nyquist criterion.
9.12
9.241. The output of the zero-force equalizer is:
qm =1∑
n=−1
cnxm−n
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With q0 = 1 and qm = 0 for m ̸= 0, we obtain the system: 1.0 0.1 −0.5−0.2 1.0 0.10.05 −0.2 1.0
c−1
c0c1
=
010
Solving the previous system in terms of the equalizer’s coefficients, we obtain: c−1
c0c1
=
0.0000.9800.196
2. The output of the equalizer is
qm =
0 m ≤ −4c−1x−2 = 0 m = −3c−1x−1 + c0x−2 = −0.49 m = −20 m = −11 m = 00 m = 1c0x2 + x1c1 = 0.0098 m = 2c1x2 = 0.0098 m = 30 m ≥ 4
Hence, the residual ISI sequence is
residual ISI = {..., 0,−0.49, 0, 0, 0, 0.0098, 0.0098, 0, ...}
and its span is 6 symbols.
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