RF System Analysis
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Transcript of RF System Analysis
1
J.Dąbrowski, Intro to RF Front-End Design1
RF-System Analysisfrom system requirements to Rx/Tx specs
• Test environment of radio system specs- Receiver analysis- Transmitter analysis
• Distribution of specs over Rx blocks• Summary
Outline
J.Dąbrowski, Intro to RF Front-End Design2
Test environment of system specs
• Frequency bands /filtering• Reference sensitivity /NF• Blocking requirements /1dB point and DR• Intermodulation requirements / IP3, IP2 and
LO phase noise• Image rejection
• Transmitted power• Out-of channel emission /filtering and LO
phase noise• Spurious tones
2
J.Dąbrowski, Intro to RF Front-End Design3
Reference sensitivity
DemodulatorPart
Digital BasebandsignalReceiver
Front-EndPin,minSNRin SNRmin
ADC
sensitivity Pin,min
BERmax SNRmin
NF = SNRin – SNRmin= Pin,min– (-174dBm/Hz + 10logB) – SNRmin
For DECT std. Pin,min= -83dBm, B = 1.728 MHz
BERmax= 10-3 → SNRmin ≈ 10dB (also for N+I)
NF = -83 + 174 -10log(1.728×106)-10 ≈ 18dB Quite relaxed
But 3..4 dB would be sacrificed for loss in duplexer and RF filter
J.Dąbrowski, Intro to RF Front-End Design4
BER versus SNR in demodulator
10-3
SNR = Psig /N = (EbR)/(N0B)
SNR = Eb/N0 × R/B
R/B ≈ 0.5 … 1.5 (often)R – bit rateB – channel bandwidth
SNRmin = (Eb/N0)dB + (R/B)dB = 12 -1.8 = 10.2 dB
(R/B)DECT = 1152/1728 = -1.8 dB
GFSK synchronous differential demodulator in DECT
Ideal GFSK synchronous demodulator (for AWGN)
3
J.Dąbrowski, Intro to RF Front-End Design5
Comment on CDMA receivers
ff
EncodingBB signal BB signal after spreading
BBB
DecodingBB signal received
Processing gain:
GP = BSS /BBB ≅ Rchip /Rdata
GP = SNRBB /SNRSS
BSS
fBBB
SNRmin = (Eb/N0)dB + (R/B)dB ≈ (Eb/N0)dB - (GP)dB
For a given demodulation scheme
Example:
For WCDMA GP = 10lg (3.84Mcps/12.2kbps) = 25dB SNRmin = (Eb/N0)dB - (GP)dB = 7dB – 25dB = -18dB
QPSK
J.Dąbrowski, Intro to RF Front-End Design6
Blocking requirements
• Desensitization• Dynamic range • Reciprocal mixing and LO
phase noise• Band and channel filtering
4
J.Dąbrowski, Intro to RF Front-End Design7
Desensitizationfor DECT
Co-channel
( ) ( )
3
123
21
223
1
23
1
33.1
12
3
...cos2
)(3)(
αα
σσαα
α
ωα
α
=
<>
−
+
+=
IP
bl
SSbl
A
A
tAtA
ty
dBmPPIIP
AA
blbl
bl
IP
33,1
2log10
12
max3
2
23
−=−
+>
−>
σ
σ
This IP3 of the RF part only, after mixer inband blockers are suppressed
-24.7dBm0.53dB
-20.4dBm0.791dB
IIP3RFσGain drop
This is kind of AM that in GMSK
J.Dąbrowski, Intro to RF Front-End Design8
1dB compression point and DR
In-band interferers must not saturate the Rx
Pbl max = -33dBm and also Psig max = -33dBm
P1dB > -33dBm, DR = P1dB – Pin,min
DR > -33 – (-83) = 50dB
P1dB
G +Pin
1dB
Pin minSensitivity
dBIIP
dBPIIP
RRAIIP
RRAP
PdB
IP
dB
4.226.933
6.9
233.1
log102
log10
2145.0
log102
log10
point compresion 1dBcalled isblocker thedrop 1For
3
dB13
30
1
0
23
3
30
1
0
2dB1
dB1
1
−=+−>
=−
==
==
αα
αα
But in practice might be different
This DR refers to the whole Rx chain.The blocker will be suppressed in BB filter, but the max signal will not.
First estimatefor Rx IP3
5
J.Dąbrowski, Intro to RF Front-End Design9
Comment on QAM systemsBER must be maintained in presence of any blocker
( )
minsigsigP
WrefP
IPSigbl
blN
SNRPN
NFBNFNN
ARAAP
−=
++−=+=
=
=
log10174
33.1,22
3
min
3
1230
2
1
23
αα
αα
E.g. for any blocker BER=10-3 → SNRminbut we have Rx Noise + blocker noise
(AM at f0 and uncorrelated)
Allowednoise for signalduring the test
Inherent Rx noise
( ) dBPIIPPP
mWPPP
P
dBsigdBbldBblN
sigIP
blblN
62
4
3
23
2
++−=
=
dBPP
PIIP
NPN
blNsigbl
sigPblNP
323
min
+−
+=
=+
Rx noise + Noise inducedby blocker
It is the Rx total IIP3, since the noise induced by blocker would not be suppressed by BB filter
This is kind of AM can be removed in GMSK Rx by amplitude clipping
J.Dąbrowski, Intro to RF Front-End Design10
Reciprocal mixing and LO phase noise
f
∫ ==H
L
f
favnn BSdffSP )(
Noise imposed:
Typically we require SIR >15dB
SIR = Psig - 10log SavB= Psig - 10log Sav - 10logB
L (foff ) = 10lg Sav - Pint = Psig – Pint - SIR - 10logB
L (1.73MHz) = -73 + 58 - 15 - 10lg(1.73·106) = -93 dBc/HzL (3.46MHz) = -73 + 39 - 15 - 10lg(1.73·106) = -112 dBc/HzL (5.18MHz) = -73 + 33 - 15 - 10lg(1.73·106) = -118 dBc/Hz
fL fH
desired
Noisy interferer at IF Sn(f )
foff
Sav
LO Phase Noise limits receiver selectivity
6
J.Dąbrowski, Intro to RF Front-End Design11
Blocking requirements (cont’d)
10-3 BER must be maintained
The Rx filters must suppress the blockers so that SNR = C/(N+I) = 10dB
Depending on Rx architecture we may have a few filters but at least the band-select and IF filter. We need an effective attenuation of at least 65..70dB provided by RF filter, LNA and BB filter
With an RF filter of 30..40dB we need another 30..40dB from LNA and BB
Attenuationrequired
J.Dąbrowski, Intro to RF Front-End Design12
Intermodulation requirements
∆P
IIP3 = ∆P/2 + Pin
Output
IIP3
Fundamental
3rd order IM
Two-tone test For DECT 2 × (Pint= -46dBm) each, and Psig= -80dBm
and still BER=10-3 → but we have Noise + IM3 (uncorrelated)
N = -83dBm - SNRmin = -93dBm (input referred thermal noise)
How much IM distortions can we allow ? → SNRmin = C/(N+I ) = 10dB
Psig,out
7
J.Dąbrowski, Intro to RF Front-End Design13
Intermodulation requirements (cont’d)
(N + PIM3 )|dBm = Psig - SNRmin = -80dBm -10dB = -90dBm ( all input referred )
(N + PIM3 )|dBm - N |dBm = -90dBm + 93dBm = 3 dB
(N + PIM3 ) / N = 2 → PIM3 = N
Hence:IIP3 = Pin + ∆P/2 ≈ - 46 + (-46+93)/2 = -22.5dBm (which is practically the same as obtained
before from the 1dB compression point )However, in zero-IF the IP2, LF feedthrough in mixer, and LO leakage would contribute as well.
RF Filter LNA LP
Filter ADC
LF feedthrough
HD2 at BB
LO LeakageWe focus on IP2 of mixer, LPF stops the interferers, and IP2 of LNA less critical
J.Dąbrowski, Intro to RF Front-End Design14
IP3 and IP2 requirementsWith this correction we have:(N + PIM3 + PIM2)|dBm = Psig - SNRmin = -80dBm -10dB = -90dBm ( all input referred )
(N + PIM3 + PIM2)|dBm - N |dBm = -90dBm + 93dBm = 3 dB
(N + PIM3 + PIM2) / N = 2 → PIM3 + PIM2 = N We allow less PIM3 to keep N
( ) ( )
mW10,5.0,12
11also and,4
42
2and,
6.4
3
2
23
3
33332
2
23
3
2
2
0
222
223
3
3
−=≈=+
++≈=+
=
==
int
intint
intint
intintint
PGNP
PG
P
P
PG
PG
PPN
PG
PG
P
P
PG
PGGR
AGGP
P
PP
FIP
F
IP
BBIP
RF
mixIP
LNA
LNAIPIPmixIPmix
RF
IP
mixIPmix
RF
RFmixRFmix
IMIP
IM
β
α
Assume all blocks contribute equally to the total IP3 and PIP2 mix = β PIP3 mix
Gain of RF filter and duplexer
8
J.Dąbrowski, Intro to RF Front-End Design15
IP3 and IP2 requirements (cont’d)
-24.7dBm0.53dB
-20.4dBm0.791dB
IIP3RFσGain drop
-2.7-22.425
-2.5-22.320
-2.1-21.915
-0.8-20.510
*) IIP3mix [dBm]IIP3 [dBm]β [dB]
*) For GLNA = 15 dB
Intermodulation requirements Single blocker requirements
Smaller β → IP2 of mixer has more impact on total (N+I) → then larger total IP3 required
How can we use the estimate for IP3RF ?
From 1dB point we also have IP3 > -22.4dBmso we conclude that the impact of mixer IP2 must be small (e.g. β = 25dB or different balance between IP3 components is needed)
We see that the demands for the IIP3RF (-24.7dBm →3dB gain drop) are too relaxed. If we only allow 1dB:
dBGIIPPG
PG
GGPG
PP
dBRFBBBBIPRF
BBIP
RF
RFRFBBIP
RF
RFIPIP
2238.151
79.01010
,11
3
3
04.224.2
*
3
*
33
−≅→≈
+≈
=+≈ σ
For GRF = 15..20 dB we obtain practical values of IIP3BB = -7dBm … -2dBm
IIP3 = -22.4dBm
Large GRF is prohibitive
J.Dąbrowski, Intro to RF Front-End Design16
Image rejection in Rx
• Homodyne (zero-IF) overcomes problems of heterodyne (esp. image problem) but suffers from DC-offset, 1/f noise, LO leakage, self-mixing, even order distortions and IQ mismatch. For WCDMA systems DC band close to 0 can be sacrificed
• Low-IF overcomes DC-offset and 1/f noise but suffers from close-image problem and even order distortions. Image-reject mixer must be used like in zero-IF, but here the IQ requirements are much tougher. BPF at IF must be used (requires 2x more poles/zeros than LPF). For narrow-band systems better than zero-IF.
4)(
)()( 22 θ+∆
==AA
PPPP
IRRinsigim
outsigim
Amplitude and phase mismatch in IQ paths
In practice IQ IRR > -40dB but -60..-70dBare sometimes needed, so filters must help,such as polyphase filters in low-IF
9
J.Dąbrowski, Intro to RF Front-End Design17
Required image rejection
for DECT
fLO for Low-IF Rx
IR = Pim in – (Psig – 15dB)
= -58 – (-73 -15) = 30dB
IR = -73 – (-73 -15) = 15dB
Low-IF Rx,
zero-IF Rx, - More relaxed requirements
J.Dąbrowski, Intro to RF Front-End Design18
Channel Filter and ADC
BPF/LPF
Pbl –A(fbl)
ADC
f0
IF×
Usually, tradeoff between ADC DR and filter order
Attenuation ↔ (foffset, filter order)
In-band blockers suppressed
LPF for zero-IF
∆fch /2 f
12 dB/oct / 2 ord
24 dB/oct / 4 ord
∆fch
36 dB/oct / 6 ordA6(∆fch )
DRADC = (Pbl – A) – (Pin min – 15dB)
PmaxQuantization noise
/ input referred
3∆fch /2
Wantedchannel for 0-IF
Adjacentchannel
GLPF
Channel selection can be completed in BB proc. but ADC must maintain the blockers
15 dB below sensitivity is a rule of thumb if 10dB for SNR is required
10
J.Dąbrowski, Intro to RF Front-End Design19
Channel Filter and ADC (cont’d)
For DECT max signal = max blocker so LP Filter playsdifferent role → mainly band limitation (Nyquist criteria)
If fS high then the requirements for the filter relaxed ( minimum is 1.8 MHz )
We have: DRADC = Pin max – (Pin min– 15dB ) = -33 –(-83-15) = 65 dB
DRADC = 6.02N + 1.76dB → N = 11 bits and if this is too large we can use VGA
VGA ADCLPF
fS
ctrl
BBproc.
ADC quantization noise,
Pq = (∆2 /12)/(R0 p) ×1000 mW p – oversampling factor = 2fS /BW for zero-IF
= VFS2 2-2NBW / (24R0 fS) ×1000 mW, ∆ - ADC resolution = VFS 2-N
J.Dąbrowski, Intro to RF Front-End Design20
ADC and Front-end gain
11bits usingwhen 6.266.9202.62) ing(oversampl 1 and ,1 Take
8.0log10log2002.6 and,4.93
1017.21010510
101010510
105 valuepracticalfor so
25
10101010
91.113.81.113.8
1.113.8min
min
min
==+−=
===
−−+−=+=
⋅=⋅⋅−
=⋅⋅−
=⇒=
=<
⋅−=
−=
+=
−−−−
−−
NdBdBNGBfVV
dBBfVNPdBPG
PPP
GNF
NFNF
NFP
NSNRNFPPSNR
G
NGNFPPGSNR
dBFE
wSFS
wSFSdBmqdBmqdBFE
qqq
FEFE
RxFE
FE
q
inFEin
qFE
inFEFEq
inFE
This are rather mild design requirements
Sensitivity and input reference noise
Very relaxed
11
J.Dąbrowski, Intro to RF Front-End Design21
Other specs of Rx / Noise floor
wHzdBmindBmBNF log10
/+=
....1
log10
1042901038.1
14
/
2123
2
==
⋅=⋅⋅
⋅==
×
+
=
=
−−
=
mWkTN
HzWK
HzKWkTN
RRRRkTRN
RinRsHzdBmin
RinRsin
inSin
inSHzWin
RS
- +
2RSV
Nin
Rin
dBm
HzdBmFdBm
6.1114.62174
10728.1log10/174 6
−=+−=
⋅+−=
RF Filter
RF Amplifier
RS = RinNoise from antenna like resistor noise. If pointed at horizon Teq=290K
For DECT Bw=1728 kHz
Matching for power
J.Dąbrowski, Intro to RF Front-End Design22
Other specs of Rx / Spurious Free Dynamic Range (SFDR)
minminmax
3max
minmin
3)3(2
when)y sensitivitRx (
SNRFIIPPPSFDR
GFPPSNRFP
inin
IMin
in
−−
=−=
+=
+=
∆P
Output
IIP3Pin,max
Pout
F+G
F
fundamental
IM3
Pin
PIM3= F+G
Pin,min
SNRmin
PIM3
Max Pin is so that PIM3 < noise floor
SFDR = 0.67(-22.4+111.6)-(10+18)= 31.8 dB required for our DECT
SFDR is a combined performance measure of Rx for noise and linearity
12
J.Dąbrowski, Intro to RF Front-End Design23
Transmitter requirements
• Max power and emission mask- noise- spur tones
• Modulation quality- SNR - constellations and EVM/ BER
J.Dąbrowski, Intro to RF Front-End Design24
Phase noise
PAMatching
& BP FilterBP
Filter
FrequencySynthesizer
f0
RF×
Modulated signal
• Close-in phase noise reduces SNR
• Far-away phase noise creates spectral emission outside the channel
• Harmonics must be avoided
• PA provides spectral regrowth due to its nonlinearities
f0
Close-in PN
Far-away PN
fRF
Transmitted signal
IF
13
J.Dąbrowski, Intro to RF Front-End Design25
Emission mask and PN• Maximum output power 250mW (24 dBm)• Maximum radiated power
M0
foff
M1
M2
M3
Channel spacing
L (foff ) = 10log Soff - P0 = Moff -10log B - M0
L (1.73MHz) = -8 - 62 - 24 = -94dBc/HzL (3.46MHz) = -30 - 62 - 24 = -116dBc/HzL (5.18MHz) = -44 - 62 - 24 = -130dBc/Hz
More stringent than for the receiver
Estimate of LO phase noise:
J.Dąbrowski, Intro to RF Front-End Design26
Distribution of specs over Rx blocks
RFFilter
LNA
LO
I Q
LPF&VGA ADC
Duplexer
Transmitterpart
For each Rx block: Gi , NFi , IP3i For LO: phase noise & spur tones
How do we distribute Rx specs over the blocks ?
14
J.Dąbrowski, Intro to RF Front-End Design27
Distribution of specs (cont’d)
...
...333
13
1
...11
321
3
21
2
1
1
21
3
1
21
×××=
+++≈
+−
+−
+=
GGGGIP
GGIPG
IPIP
GGNF
GNFNFNF
Only approximate formula for IP3
If the blocks are not impedance matched, corrections needed
Observe that distribution of gain to maintain low NF and high IP3 (or IP2) is contradictory.
Largest signal or a blocker must not saturate LNA, mixer or IF filter.Often LNA requires gain control as well to avoid saturation of the following stages. Using VGA before ADC is typical.
J.Dąbrowski, Intro to RF Front-End Design28
Summary
• First order specs can be retrieved from system requirements
• Simulation models needed for verification• In case of integrated TRx’s the blocking and
intermodulation requirements are more stringent than for Rx /leakage, substrate coupling, and radiation of Tx power/ Digital part even more noisy
• Distribution of specs depended on the available RF blocks and architecture, many constraints, little degree of freedom usually