DSP Group, EE, Caltech, Pasadena CA1 Beamforming Issues in Modern MIMO Radars with Doppler Chun-Yang...
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Transcript of DSP Group, EE, Caltech, Pasadena CA1 Beamforming Issues in Modern MIMO Radars with Doppler Chun-Yang...
DSP Group, EE, Caltech, Pasadena CA 1
Beamforming Issues in Modern MIMO Radars with Doppler
Chun-Yang Chen and P. P. Vaidyanathan
California Institute of Technology
DSP Group, EE, Caltech, Pasadena CA 2
Outline Review of the MIMO radar
Spatial resolution. [D. W. Bliss and K. W. Forsythe, 03]
MIMO space-time adaptive processing (STAP) Problem formulation Clutter rank in MIMO STAP Clutter subspace in MIMO STAP
Numerical example
DSP Group, EE, Caltech, Pasadena CA 3
SIMO RadarTransmitter: M elements Receiver: N elements
dT
ej2(ft-x/)
w2 w1 w0
dR
ej2(ft-x/)
Transmitter emits coherent waveforms.
Number of received signals: N
DSP Group, EE, Caltech, Pasadena CA 4
Transmitter: M elements Receiver: N elements
dT
ej2(ft-x/)
dR
ej2(ft-x/)
MF MF…
…
Transmitter emits orthogonal waveforms.
Matched filters extract the M orthogonal waveforms.
Overall number of signals: NM
MIMO Radar
DSP Group, EE, Caltech, Pasadena CA 5
Transmitter: M elements Receiver: N elements
Virtual array: NM elements
dT=NdR
dR
ej2(ft-x/) ej2(ft-x/)
MF MF…
…
MIMO Radar (2)
The spacing dT is chosen as NdR, such that the virtual array is uniformly spaced.
DSP Group, EE, Caltech, Pasadena CA 6
The clutter resolution is the same as a receiving array with NM physical array elements.
A degree-of-freedom NM can be created using only N+M physical array elements.
Receiver: N elements
Virtual array: NM elements
Transmitter : M elements
+ =
[D. W. Bliss and K. W. Forsythe, 03]
MIMO Radar (3)
DSP Group, EE, Caltech, Pasadena CA 7
Space-Time Adaptive Processing (STAP)
vvsini
airborne radar
jammertarget
i-th clutter
vt
ii
Di
vf
c
vf
sin2sin2'
The clutter Doppler frequencies depend on looking directions. The problem is non-separable in space-time.
i
The adaptive techniques for processing the data from airborne antenna arrays are called space-time adaptive processing (STAP).
DSP Group, EE, Caltech, Pasadena CA 8
Formulation of MIMO STAP
1,,1,01,,1,01,,1,0,,,,,,,,,,
LlMmNn
wvcsy lmnlmnlmnlmnlmn
dT=NdR
ej2(ft-x/)
dR
ej2(ft-x/)
MF MF……
Transmitter : M elements Receiver: N elements
vsin vsin
target
vt
targetvt
target
IRRssR
wvcsy
vcy2
H
clutterjammer
noiseNML
NML x NML
DSP Group, EE, Caltech, Pasadena CA 9
c ii
Ti
RN
i
vTlj
dmj
dnj
ilmn eeec1
sin22sin2sin2
,,
Clutter in MIMO Radar
)(2,,,
, lmnfjlmni
isec
RR
T
iR
is
d
vT
d
d
df
2
sin,
cN
i
Hiiic
HE1
2,][ ccccRc
cN21c cccR span)(range
cN
iii
1
cc size: NML
size: NMLxNML
lmni
N
iic
c
,,,1
DSP Group, EE, Caltech, Pasadena CA 10
Clutter Rank in MIMO STAP: Integer Case
Integer case: and are both integers.
)}.1()1(1,,1,0{ LMNlmn
),),1()1(min()(rank cNNMLLMN cR
This result can be viewed as the MIMO extension of Brennan’s rule.
Theorem: If and are integers,
The set {n+m+l} has at most N+(M-1)+(L-1) distinct elements.
)(2,,,
, lmnfjlmni
isec cN21c cccR span)(range
DSP Group, EE, Caltech, Pasadena CA 11
Clutter Signals and Truncated Sinusoidal Functions
.)(2,,,
, lmnfjlmni
isec ci is NML vector which consists of
)1()1(1,5.0
otherwise.,0
0,),(
,
2
,
,
LMNXW
WfW
Xxexfc
is
xfj
is
is
It can be viewed as a non-uniformly sampled version of truncated sinusoidal signals.
-50 0 50 100 150-1
-0.5
0
0.5
1
x
c(f s,
i),x)
-1 -0.8 -0.6 -0.4 -0.2 0 0.2 0.4 0.6 0.8 10
20
40
60
80
100
fs
|C(f s,
i,f s)|
(b)
The “time-and-band limited” signals can be approximated by linear combination of prolate spheroidal wave functions.
X
2W
DSP Group, EE, Caltech, Pasadena CA 12
Prolate Spheroidal Wave Function (PSWF)
Time window Frequency window
X -W W0
Prolate spheroidal wave functions (PSWF) are the solutions to the integral equation [van tree, 2001].
in [0,X]
Only the first 2WX+1 eigenvalues are significant [D. Slepian, 1962].
The “time-and-band limited” signals can be well approximated by the linear combination of the first 2WX+1 basis elements.
DSP Group, EE, Caltech, Pasadena CA 13
PSWF Representation for Clutter Signals
WfW
Xxexfc
is
xfj
is
is
,
2
, otherwise.,0
0,),(
,
-50 0 50 100 150-1
-0.5
0
0.5
1
x
c(f s,
i),x)
-1 -0.8 -0.6 -0.4 -0.2 0 0.2 0.4 0.6 0.8 10
20
40
60
80
100
fs
|C(f s,
i,f s)|
(b)
)1()1(12
)1()1(1,5.0
)(),(2
0,,
LMNWX
LMNXW
xxfcWX
kkkiis
The “time-and-band limited” signals can be approximated by 2WX+1 PSWF basis elements.
clutter rank in integer case
DSP Group, EE, Caltech, Pasadena CA 14
PSWF Representation for Clutter Signals (2)
WX
kkkiis xxfc
2
0,, )(),(
WX
kkkilmni lmnc
2
0,,,, )(
Tkkk
Ti LMN ))1()1(1()0(( ccc
1-L1,-M1,-Ni,i,1,0,0i,0,0,0 uc
1
0,
cr
kkkii uc )1()1(12 LMNWXrc
The PSWF (x)can be computed off-line
The vector uk can be obtained by sampling the PSWF.
non-uniformly sample
1211
2, ,
c
c
rH
N
i
Hiiic uuuUUAUccRc
U: NML x rc A: rc x rc
DSP Group, EE, Caltech, Pasadena CA 15
)(2,,,
, lmnfjlmni
isec
xfjis
isexfc ,2, ),(
)(xk
i-th clutter signal
truncated sinusoidal PSWF
Non-uniformlysample
Linearcombination
Non-uniformlysample
)( lmnk Sampled PSWFLinear
combination
Stack
ici-th clutter signal
Stack
kuSampled PSWFLinear
combination
HN
i
Hiiicc
c
R UAUcc
1
0
2 ,
Clutter covariance matrix
U: NML x rc A: rc x rc
)1()1( LMNrc
DSP Group, EE, Caltech, Pasadena CA 16
Numerical Example
0 20 40 60 80 100 120 140 160 180 200
-200
-150
-100
-50
0
50
100
Basis element index
Clu
tter
pow
er (
dB)
Proposed subspace methodEigen decomposition
N+(M-1)+(L-1)
N=10M=5L=16=N=10NML=800N+(M-1)+(L-1)=72.5
Proposed method
Eigenvalues
The figure shows the clutter power in the orthonormalized basis elements.
The proposed method captures almost all the clutter power.
Parameters:
k
qkH Rcqk
DSP Group, EE, Caltech, Pasadena CA 17
Conclusion The clutter subspace in MIMO radar is explored.
Clutter rank for integer/non-integer and Data-independent estimation of the clutter subspace.
Advantages of the proposed subspace estimation method. It is data-independent. It is accurate. It can be computed off-line.
DSP Group, EE, Caltech, Pasadena CA 18
Further and Future Work Further work
The STAP method applying the subspace estimation is submitted to ICASSP 07.
Future work In practice, some effects such as
internal clutter motion (ICM) will change the clutter space.
Estimating the clutter subspace by using a combination of both the geometry and the data will be explored in the future.
-0.5 -0.4 -0.3 -0.2 -0.1 0 0.1 0.2 0.3 0.4 0.5 -16
-14
-12
-10
-8
-6
-4
-2
0
Normalized Doppler frequency
SIN
R (
dB)
SMI, K=2000LSMI, K=300
PC, K=300
Separate, Kv=20, K
c=300
New method ZF, Kv=20
New method, Kv=20, K
c=300
MVDR, perfect Ry
New method
DSP Group, EE, Caltech, Pasadena CA 19
References
[1] D. W. Bliss and K. W. Forsythe, “Multiple-input multiple-output (MIMO) radar and imaging: degrees of freedom and resolution,” Proc. 37th IEEE Asilomar Conf. on Signals, Systems, and Computers, pp. 54-59, Nov. 2003.
[2] D. Slepian, and H. O. Pollak, "Prolate Spheroidal Wave Functions, Fourier Analysis and Uncertainty-III: the dimension of the space of essentially time-and-band-limited signals," Bell Syst. Tech. J., pp. 1295-1336, July 1962.
[3] D. J. Rabideau and P. Parker, "Ubiquitous MIMO Multifunction Digital Array Radar," Proc. 37th IEEE Asilomar Conf. on Signals, Systems, and Computers, pp. 1057-1064, Nov. 2003.
[4] N. A. Goodman and J.M. Stiles, "On Clutter Rank Observed by Arbitrary Arrays," accepted to IEEE Trans. on Signal Processing.
DSP Group, EE, Caltech, Pasadena CA 20
Thank you
DSP Group, EE, Caltech, Pasadena CA 21
Comparison of the Clutter Rank in MIMO and SIMO Radar
MIMO SIMO
Clutter rank N+(M-1)+(L-1) N+(L-1)
Total dimension
NML NL
Ratio (=N)
NML
1)-(L
L
1 <
The clutter rank is a smaller portion of the total dimension. The MIMO radar receiver can null out the clutter subspace
without affecting the SINR too much.
>
>
NL
1)-(L
L
1
DSP Group, EE, Caltech, Pasadena CA 22
Formulation of MIMO STAP (2)
)sin(2
2)sinsin(2
,,
vvTlj
dm
dnj
lmn
tt
Tt
R
ees
lfjmnfj tDts ee , , 2)(2
R
T
ttD
tR
ts
d
d
Tvv
f
df
)sin(2
sin
,
,
dT
ej2(ft-x/)
dR
ej2(ft-x/)
MF MF……
Transmitter : M elements Receiver: N elements
vsin vsin
target
vt
targetvt
T: Radar pulse period
DSP Group, EE, Caltech, Pasadena CA 23
Fully Adaptive STAP for MIMO Radar
1 subject to
min
sw
wRw yw
H
H
lfjmnfjlmn
tDts ees , , 2)(2,,
sRs
sRw
y
y
1
1
H
K
k
HkkK 1
1yyRy
^
Difficulty: The size of Ry is NML which is often large. The convergence of the fully adaptive STAP is slow. The complexity is high.
Solution:
DSP Group, EE, Caltech, Pasadena CA 24
Clutter Subspace in MIMO STAP: Non-integer Case Non-integer case: andnot integers.
Basis need for representation of clutter steering vector ci.
Data independent basis is preferred. Less computation Faster convergence of STAP
We study the use of prolate spheroidal wave function (PSWF) for this.
DSP Group, EE, Caltech, Pasadena CA 25
Extension to Arbitrary Array
))1(2)(
)((max(2
1)(rank
',,
',,1,',,',
1
))2((2
,,
,,
LT
ec
mRmR
nRnRT
mmnn
N
i
Tlj
ilmn
cmTnR
Ti
vxx
xxuRu
c
vxxu
This result can be extended to arbitrary array.
XR,n is the location of the n-th receiving antenna.XT,m is the location of the m-th transmitting antenna.ui is the location of the i-th clutter.v is the speed of the radar station.
DSP Group, EE, Caltech, Pasadena CA 26
Review of MIMO radar: Diversity approach
dR
ej2(ft-x/)
MF MF…
…
Receiver: If the transmitting antennas are f
ar enough, the received signals of each orthogonal waveforms becomes independent. [E. Fishler et al. 04]
This diversity can be used to improve target detection.
DSP Group, EE, Caltech, Pasadena CA 27
Prolate Spheroidal Wave Function (PSWF) (2) By the maximum principle, this basis concentrates most of its en
ergy on the band [-W, W] while maintaining the orthogonality.
Only the first 2WX+1 eigenvalues are significant [D. Slepian, 1962].
The “time-and-band limited” signals can be well approximated by the linear combination of the first 2WX+1 basis elements.
DSP Group, EE, Caltech, Pasadena CA 28
Review of MIMO Radar: Degree-of-Freedom Approach
The clutter resolution is the same as a receiving array with NM physical array elements.
A degree-of-freedom NM can be created using only N+M physical array elements.
Receiver: N elements
Virtual array: NM elements
Transmitter : M elements
dT=NdR
ej2(ft-x/)
dR
ej2(ft-x/)
MF MF……
+ =
[D. W. Bliss and K. W. Forsythe, 03]