Adcom’s GFP-565 Preamplifier, Part 4 - Walt · PDF filedcom’s GFP-565 preamplifier...

Adcom’s GFP-565 preamplifiercame with an excellent phonopreamp designed by WaltJung. The circuit (Fig. 8) is no

secret, since Linear Technology pub-lished a nearly identical topology onthe front page of their LT 1115 op-ampdata sheet (I thank Victor Campos forgranting permission to reproduce thecircuit back when he was Vice Presi-dent for Product Development atAdcom).

The gain block is a Linear Technolo-gy LT1028C op amp (Adcom 8A, andpredecessor to the LT1115), buffered bythe high-current LT1010CT video buffer(Adcom 1A). R119, the 49.9Ω bias resis-tor, sets the LT1010 output stage forpure Class-A operation. D101, a J555JFET current source, forces the LT1028output stage into Class-A operation.The LT1028 was the quietest op ampavailable when the 565 preamp was de-signedvoltage noise was specified at1.1nV√Hz at 1kHz. To keep the preampnoise as low as possible, the 565 phonopreamp has a low impedance RIAAfeedback loop.

The LT1010 buffer provides plenty ofoutput current for linear drive of thelow-Z network. C107 (bypassed by filmcap C109) keeps the DC gain at unity,making the DC offset manageable. TheLT1028C has very low input bias cur-rent (for a bipolar-input device), andlow DC offset, allowing DC coupling ofthe output (R115 provides a slight offsettrim for the circuit).

The RIAA network capacitorsC111,C113, and C115are 1% tolerance Roed-erstein KP-series polypropylene types.The 565 phono preamp has excellentRIAA accuracy, ±0.1dB, 20Hz−20kHz.

This was a very fine phono preamp bylate-1980s standards, and it would bevery easy for a modifier to make itworse. A “safe” modification might con-sist of simply replacing the 1% Roeder-stein/Resista MK2 resistors with bettertypes.

So why design anew phono preamp?The original Adcomtopology has one soniclimitation that can’t befully solved with partssubstitutions. Thebiggest sonic snags inthis design are theelectrolytic caps thatkeep the gain unity atDC. My goal in design-ing the new phonopreamp was to elimi-nate these capacitorsby using a gain blockwith lower offset andlower input bias cur-

rent, and controlling the residual DCoffset with a servo.

I settled on Analog Devices’ AD745J,an FET-input op amp with ultra-lowvoltage noise (2.9nV√Hz at 1kHz) and12.5V/µS slew rate (compared to 11V/µSfor the LT1028). Typical input offsetvoltage is 0.25mV, and input bias cur-rent is 150pA.

The input bias current is the criticalspec. The LT1028C specifies this as40nA. The significantly lower input biascurrent of the AD745 maintains stable

This final installment describes the new phono preamp. By Gary Galo

Adcom’s GFP-565 Preamplifier, Part 4

24 audioXpress 2/04 www.audioXpress.com

56

73

2J1

++

IC101LT1028C

C1174700pF

C11515000pF

C1113300pF

C1131000pF

C101100pF

IC103

-18V

+18V

+ C1094.7uF

OUTPUT TO S206/S207

BIAS

R11949.9

R117475

R107261

R113215k

R11117.8k

R109499

R10347.5k

R121100

R11582.5k

FIGURE 8: The original Adcom phono preamp. The pre-amp uses a Linear Technology LT1028 op amp bufferedby an LT1010 video buffer. Linear Technology publisheda nearly identical circuit in the datasheet for the LT1115.

A-2313-8

PHOTO 32: The modified phono preamp before the installation of the DC servo. C107through C110 have been removed, and the LT1010 heatsinks have been replaced.

DC offset with source impedances rang-ing from very low-Z phono cartridges(below 100Ω) to the 47k cartridge termi-nating resistor. I believe that it’s impor-tant to maintain safe DC operating lev-els even with the cartridge unplugged.

The excellent DC characteristics ofthe AD745 are possible because of theFET-input design. FET-input op ampsare normally too noisy for high-gain cir-cuits such as phono preamps. But theAD745 achieves its excellent noise per-formance with large-geometry FETs inthe front end (the metallization photoshows that the FET differential inputtakes up well over one-third of the diespace). The trade-off, as far as die spaceis concerned, is a less robust outputstage than some other devices. But,buffering the op amp overcomes thislimitation.

The AD745 does have higher voltagenoise than the LT1028, but my measure-ments indicate that the new phono pre-amp is actually quieter than the Adcomoriginal. This is probably due to the sub-stantially lower current noise of theAD745, which results in lower measuredphono noise with a low-Z source. Youcould use a current-feedback amplifiersuch as the AD811 or the discontinuedBUF04 for the output buffer. However, Istill like the sonic characteristics of theLT1010 in this application, so I retainedit. I lowered the bias resistors to 33Ω,which improved the sonics of the

LT1010 even fur-ther, but also re-quires additionalheatsinking.

STABILITY ISSUESMany op amps de-signed for high-gain applicationsare not unity-gainstable. The LT1028is stable at voltagegains of two orhigher (it can beused in unity-gainapplications, withcertain caveats de-scribed in the datasheet). AlthoughRIAA preampli-fiers normallyhave very highvoltage gains atlower frequencies,at high frequen-cies the gain will eventually fall to unityand below as the reactances of the RIAAfeedback capacitors approach zero.

A “gain-stop” resistorR109 in theAdcom circuitis added to prevent thevoltage gain from falling below safe lev-els. You can determine the minimumhigh-frequency voltage gain in theAdcom circuit with the same formulaused to calculate the voltage gain of

any non-inverting amplifier:

Gain = R109/R107 + 1

The values used in the Adcom circuitprevent the voltage gain from fallingbelow 2.9.

The AD745J is designed to operate atvoltage gains of five or higher, so the val-ues of R109 and R107 will not work. You

DC SERVO BOARD

6 4 3

(**IC106)

(**R152)

(**R154)

(**C154)

(**R157)

(C112)

(**C114a)

(*IC102)TO S206/S207

* = New Value and/or New Type** = New PartLeft Channel Shown.Right Channel Designatorsare in Parentheses ( ).

(**R118)

(*R112) (*R114)

(*C114)

(C116)

(*R110)

(IC104)

2

3

4

7

6 13

5

(*R108)

R111 & R112 = 17.4K + 200R113 & R114 = 210k + 1k

(C118)

LOCAL BYPASSING

+14V

4700pF

C115

15000pF

C111

3300pF

*C113

680pF

*IC101

**C113a

220pF

LT1010

IC103

C101

100pF

PHONO IN

OUTPUT

+ **C155100uF

+ **C156

**C1571uF

**C1581uF

+14V

-14V

-14V

**C151 (**C152)

0.22uF

**C153

0.22uF

**IC105

*R11933

*R117

332

*R107

121

*R113

211k

*R111*R109

499

*R103

47.5k

*R121

100

1.5Meg

**R151

499k

**R153

499k

FIGURE 10: An alternatephono preamp with 45.5dBof gain. This preamp issuitable for cartridges withoutputs around 2mV. A-2313-10

G. Galo: Buffered, Isolated RIAA Emphasis Network.IcVs2 Scaling = 0.10103/(10^[(1kHz Gain in dB)/20])

-14V

+++

IC103

C101100pF

C113a470pF

C111a

++

IC101

C2511000pF

OP97EPIC105

C1131000pF

C1112200pF

C11515000pF

C1176800pF

-14V

+

-

IcVs17.5e4

+

-

+

-

VcVs12.862e6

C11nF1kHz

-1/1V+

-

IcVs20.000998735

C21nf

C1530.22uF

C151 0.22uF

+14V

R121100

R205475

R10347.5k

R1091k

R11117.1k

R113211k

R107221

R117510 VR201/VR204

25k

R2318k

R12.862e6

R375k

R153499k

R151499k

R1551.5Meg

FIGURE 11: Simulation circuit for RIAA analysis of the phonopreamps. The circuit on the bottom is a mathematically idealRIAA emphasis model. Final values for R117 and C117 were de-termined in conjunction with the line stage loading.

A-2313-11

DC SERVO BOARD

(C102)

DC SERVOLOCAL BYPASSING

(or 511)

R111 & R112 = 15K + 2.1kR113 & R114 = 210k + 1k

(*R118)

(C114)

(**C112a)

**C114a

(*R108)

53

16

7

4

3

2

(*R110)

(C116)(*C112)

(*R114)(*R112)

(*R120)

(*R122)(*R104)

* = New Value and/or New Type** = New PartLeft Channel Shown.Right Channel Designatorsare in Parentheses ( ).

TO S206/S207(*IC102)

(**C154)

(**R154)

(**R152)

(**IC106)

34

+14V

*C117

6800pF

C115

15000pF

*C111

1000pF

++ AD745J

**C111a

680pF

IC103

-14V

C101

100pF

PHONO IN

OUTPUT

**C113a

470pF

-14V

+14V

**C1581uF

**C1571uF

+ **C156100uF

+ **C155100uF

-14V

0.22uF

**C153

0.22uF

**IC105

*R11933

*R117

510

*R107

221

211k17.1k

*R109

1k

*R103

47.5k

*R121

100

**R151

499k

**R153

499k

FIGURE 9: The new40dB phono preamp.An AD745J FET–inputop amp is buffered bythe original LT1010,with DC–servo control. A-2313-9


could drop R107 to 121Ω, satisfying theAD745J’s stability requirement, and rais-ing the 1kHz gain of the circuit from theoriginal 40dB to 45dB. This would befine for lower-output cartridges (2 to2.5mV), but moving magnet cartridgeswith outputs in the 5mV range wouldlikely overload the preamp. Early on inmy work with the AD745J in this circuit,I did drop R107 to 121Ω, which workedfine with my Grado Signature XTZII andAdcom XC-MRII cartridges. But, manybuilders would not find the 45dB pre-amp suitable.

I’m sure that many readers of aX arefamiliar with Stanley Lipshitz’s 1979AES paper “On RIAA Equalization Net-works” (required reading for anyone de-signing RIAA phono preamps1). As theLipshitz math shows, you can’t add again-stop resistoror change thevaluewithout seriously affecting theRIAA accuracy. An RIAA network mustbe designed with this resistor takeninto account, and any change in this re-sistor requires a redesign of at leastpart of the network.

The Lipshitz math is quite daunting,but you don’t have to be a mathemati-cian to make it work. A few years ago Idesigned a group of spreadsheets,using Microsoft Excel, to do the calcu-lations for all four feedback RIAAtopologies described in the Lipshitz ar-ticle. With the spreadsheets to do thework, accurate RIAA design has be-come easy and painless. I use thespreadsheets along with SPICE-basedcircuit simulation in CircuitMaker2000, which is my primary schematiccapture and simulation program2.

NEW PHONO PREAMPSWith the Lipshitz math in hand, I decid-ed to redesign the Adcom RIAA cir-cuits, and offer preamps with both 40dBand 45.5dB of gain. The RIAA feedbackvalues are close to the original values,since I retained the large 15,000pF ca-pacitor C115 (C116 in the right channel;for the rest of this article, parts designa-tors in parentheses refer to the rightchannel).

Figure 9 shows the 40dB circuit andFig. 10 shows the 45.5dB circuit. Inboth preamps R109 ensures that thegain will never drop below five at highfrequencies. It was not possible to getexact RIAA values from single, off-the-

shelf parts. R111 and R113 are eachmade from two resistors in series. Fourparallel capacitors are needed for the40dB preamp; this number drops tothree for the 45.5dB preamp. TheAdcom PC layout accommodates onlytwo capacitors in these locations, butyou can easily solder the additional par-allel caps to the bottom of the PC board.

The servo amplifier is an Analog De-vices OP97EP, a device Walt Jung sug-gested for this application. The integra-tor R/C values produce a −3dB point of0.22Hz for the preamps, and shouldkeep the DC offset at low levels regard-

less of source impedance (I thank Waltfor suggesting the integrator resistorvalues).

SIMULATIONSFigure 11 shows my schematic for simu-lating the accuracy of the RIAA preamp-lifiersthe 40dB preamp is shown here.The circuit at the bottom is a SPICEmodel for a mathematically ideal RIAAemphasis network, with the bass andtreble portions of the network isolatedto prevent interaction. I based this net-work on an RIAA de-emphasis networkWalt Jung designed(see sidebar).

audioXpress February 2004 27

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At the time, he was doing RIAA simu-lation by comparing the outputs of aphono preamp design and a mathemati-cally ideal de-emphasis network. But,CircuitMaker 2000 doesn’t seem to sup-port this (though CircuitMaker Version6 did), so I essentially inverted hismodel to produce the emphasis modelin Fig. 11. There seems to be a problemwith Analog Devices’ SPICE model forthe OP97 op amp. I used the model forthe OP297, which is the dual version ofthe OP97.

R1/R2/C1 set the mid- and low-fre-quency time constants at 3180µS and318µS. R3/C2 sets the treble time con-stant at 75µS. With isolated networks,you don’t need the Lipshitz math, sincethere are no interactions between thetreble and bass networksjust plug inthe real-time constants to determinethe component values. VcVs1 and IcVs1are scaled to match the series resis-tances that follow each device.

The IcVs2 scaling adjusts the outputof the emphasis model to match thegain of the preamp. This applies 10mVto the input of the phono preamp, andmakes the frequency response simula-tion curve lie around 0dB on the “Y”axis. Use this formula to determine theICVs2 scaling:

IcVs1 Scaling = 0.10103/10[(1kHz gain in

dB)/20]

The exact 1kHz gain of the 40dB pre-amp is 40.3, but this drops to 40.1dBwith the line stage loading, so the re-quired scaling is 0.000998735. For the45.5dB preamps, the actual gain withline stage loading is 45.375dB, for ascaling of 0.000544127.

Figures 12 and13 show the simu-lated RIAA accu-racy for the 40dBand 45.5dB pre-

amps. Cursors 1 and 2 are set to the low-est and highest points in the curve be-tween 20Hz and 20kHz. The horizontaldashed lines mark the total spread ofthe error, which is around 0.012dB forboth preamps. These circuits are accu-rate to within ±0.006dB (yes, that’s sixthousandths of a dB!), 20Hz to 20kHz.

Have I gotten carried away? I don’tthink so. The curves in Figs. 12 and 13


1.000 Hz 10.00 Hz 100.0 Hz 1.000kHz 10.00kHz 100.0kHz

100.00mdB

50.00mdB

0.000mdB

-50.00mdB

-100.0mdB

-150.0mdB

-200.0mdB

-250.0mdB

A: c251_2

FIGURE 12: Simulated response of the 40dB phono preamp. Thesimulation shows the response to be accurate ±0.006dB, 20Hzto 20kHz. The tight simulated response ensures good resultswith real–world component tolerances.

A-2313-12


100.00mdB

50.00mdB

0.000mdB

-50.00mdB

-100.0mdB

-150.0mdB

-200.0mdB

-250.0mdB

A: vr201_2

FIGURE 13: Simulated response of the 45.5dB phono preamp.The simulation shows the response to be accurate ±0.006dB,20Hz to 20kHz.

A-2313-13

40dB Phono Preamp - RIAA Response

-0.500

-0.400

-0.300

-0.200

-0.100

0.000

0.100

0.200

0.300

0.400

0.500

20 50 100 500 1k 5k 10k 15k 20k

Frequency in Hz

Res

po

nse

in d

B

Left Channel Right Channel

FIGURE 14: Measured response of the 40dB phono preamp. Thegraph was produced with a spreadsheet, taking errors in thegenerator, voltmeter, and inverse RIAA network into account.The response is accurate ±0.04dB, 20Hz to 20kHz.

A-2313-14

-0.500

-0.400

-0.300

-0.200

0.200

0.300

0.400

0.500

20 50 100 500 1k 5k 10k 15k 20k

Frequency in Hz

Res

po

nse

in d

B

Left Channel Right Channel

FIGURE 15: Measured response of the 45.5dB phono preamp.This preamp is accurate ±0.08dB, 20Hz to 20kHz.

A-2313-15

PHOTO 33: Bottom view of the phono preamp showing power supply connections to the DCservo, and parallel capacitors for the RIAA networks. C109 and C110 are replaced withjumpers.

can only be realized with zero percenttolerance components, which is impos-sible in the real world. The best thatyou can do with real-world componentsis 1% resistors and the 2.5% Wima FKP-2 capacitors sold by Welborne Labs.

My designs retain some of the 1% ca-pacitors (C115) from the original Adcomcircuit, which helps. But unless you’re amanufacturer, 1% tolerances for the re-maining caps will be prohibitively ex-

pensive, and generally unavailable inquantities less than 1000 per value. TheLipshitz math, with the help of myspreadsheet, makes it possible to designextremely accurate RIAA networksquickly and easilyit is really no moretime-consuming to design a good onethan a bad one. So why not do it right?

The Wima FKP-2 polypropylene ca-pacitors are of the same type and con-struction as the Roederstein KP-series

Adcom used, so there’s no prob-lem using them with some of theoriginal Adcom capacitors. Ihand-selected the 2.5% capacitorsI bought from Welborne on myBK Precision 875B LCR meter,which has 1% accuracy. I foundthat out of six or eight 3.5% Wimacaps, at least two measured closeto dead-on. The Wima caps arefairly inexpensive, which makesthis a practical approach.

The extremely tight accuracyin the simulation will ensure thatthe end result will still be verygood with real-world compo-nents. Ideally, I’d like to see a fin-ished product with an accuracy

of ±0.1%. Since the late 1970s, thereseems to be general agreement in boththe “golden ear” and “scientific” campsthat this level of accuracy will ensurethat the frequency response errors ofthe RIAA circuit will not be audible. Ifyou start out with accuracy of ±0.1% in asimulation, the end result will probablybe quite unacceptable.

My simulations required three devia-tions from the ideal RIAA network val-ues, as determined by the Lipshitzmath. First, the capacitors in the trebleportion of the network (C111, C113, andso on) were trimmed to compensate forthe loop-gain error of the AD745J. Sec-ond, R113 needed to be adjusted slight-ly to compensate for the impedance ofthe DC servo.

I made these adjustments with circuitsimulation after determining the nomi-nal values using the Lipshitz math. Fi-nally, I decided to treat the line stageloading as part of the circuit, includingthe bandwidth-limiting networkR205/C251, along with the 25k load ofthe balance and volume controls. Theoutput R/C network R117 and C117 wastrimmed with circuit simulation to pro-


PHOTO 34: Close–up of the AD745JR in the SOICpackage mounted on an Aries SOIC–to–DIPadapter. The four pins on each end of the op ampare cut off, and a solder bridge between pins 3and 4 makes the connection to the inverting input.

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duce the flattest high-frequency re-sponse with the line stage loading aspart of the system, with the output takenat the junction of R205 and C251.

This approach will produce optimumhigh-frequency accuracy only with thephono preamp connected to the linestage with the listening selector switch.This may be of concern to those whotape LP records. If you put the record-ing selector on phono and the listeningselector in some other position, therewill be a high-frequency error in theRIAA response at the tape outputs. But,if recording LPs while monitoring yourrecorder is a necessary part of youraudio life, you can change R117 to 590Ωin the 40dB preamp, and 432Ω in the45.5dB preamp.

BUILDING THE RIAA PREAMPSBefore you order parts, you’ll need tomake the same choice for the resistorsthat you did for the line stage in part 3.My recommendations are the same asbefore. Some of the photos show a mix ofHolco H4 and the Vishay-Dale CMF RN-60 types. After I had switched from ca-pacitor-coupled outputs to DC servo con-trol, I made the necessary changes in thecircuits only to find that the Holco val-ues I needed were no longer available.

Ideally, I recommend using the sametype of resistor throughout, with a cou-ple of exceptions. The 33Ω bias resis-tors need not be exoticthe Vishay-Dale resistors are fine here. There’salso no need to use anything more ex-pensive than the Vishay-Dale or Holcoresistors in the servo.

For the remaining resistors, I builtone preamp with Caddock MK132s andtwo others with Holcos and Vishay-Dales. The Caddock resistors are reallystellar in these circuits, but the otherresistors still perform extremely well. Ifyou use Holco resistors, you’ll need tostand them on end, as you did for part3. Use sleeving on the exposed leads.

Analog Devices has discontinued the8-pin DIP AD745JNthey now offer thischip only in a 16-pin SOIC package,which they call the AD745JR-16. Youcan use the AD745JR-16 with the sameAries SOIC to-DIP adapter used in theregulator in part 2 (the 16-pin SOICpackage is too wide to fit the AccutekMicrocircuit adapter). But, you may stillbe able to buy the AD745JN.

Rochester Electronics specializes indiscontinued semiconductors frommost of the major manufacturers. As ofthis writing, they still had 13,800AD745JN op amps in stock. With a $50minimum order, you may considermany other devices of interest, includ-ing BUF04s and BUF03s.

COMMON STEPSBegin construction with steps that arecommon to both the 40dB and 45.5dBpreamps (Photos 32 and 33). For a fewof the resistor replacements in thesepreamps, you’ll use the same value, butsubstitute a new type.

• Remove D101 (D102; these partswon’t be replaced).

• Remove R115 (R116; these partswon’t be replaced).

• Replace R103 (R104) with 47.5k.• Replace R121 (R122) with 100Ω.• Replace R119 (R120) with 33Ω

Vishay-Dale CMF type RN60.

• Remove C107 (C108; these partswon’t be replaced).

• Remove C109 (C110; these partswon’t be replaced).

• Install jumpers in the C109 and C110footprints on the bottom of the PCboard (Photo 33).

Feel free to change C101 (C102) tosuit the loading requirements of yourphono cartridge, taking the capaci-tance of your tonearm cable into ac-count. Use Wima FKP-2 capacitorsfrom Welborne Labs.

Perform the following step if you areusing the 8-pin DIP AD745JN:

• Replace IC101 (IC102) with theAD745JN.

Perform the following steps if you areusing the 16-pin SOIC AD745JR-16(Photo 34):

• Cut off the four pins on each end ofthe AD745JR-16 op amps. These arepins 1, 2, 7, 8, 9, 10, 15, and 16. The


TABLE 1MEASUREMENTS ON 40dB SAMPLE BUILT FOR C. VICTOR CAMPOS

S.N.AC14755LEFT PHONO TO TAPE OUT LEFTTHD (W/JUNG-LIPSHITZ INVERSE RIAA NETWORK; 2V OUT)

WIDEBAND W/80KHZ LP FILTER20Hz 0.0022% 0.0016%1kHz 0.0023% 0.0017%10kHz 0.0033% 0.0029%20kHz 0.0047% 0.0046%

RIGHT PHONO TO TAPE OUT RIGHTTHD (W/JUNG-LIPSHITZ INVERSE RIAA NETWORK; 2V OUT)

WIDEBAND W/80KHZ LP FILTER20Hz 0.0022% 0.0016%1kHz 0.0023% 0.0017%10kHz 0.0032% 0.0029%20kHz 0.0047% 0.0046%

PHONO TO TAPE OUT SMPTE (4:1) 1:1(2V IN > 2V OUT)Left 0.00175% 0.0016%Right 0.0015% 0.0012%

Phono signal-to-noise ratio (relative to 2V out @ 1kHz)−94.5dB Unweighted (left and right channels identical)All measurements made with Sound Technology 1700B By Gary Galo, 11/2/2002

PHOTO 35: Method for soldering resistors in series. Caddock MK132 are shown on theleft, and Vishay–Dale on the right. Series resistors are necessary to get the exact valuesneeded for the RIAA feedback network.

eight remaining pins are 3, 4, 5, 6, 11,12, 13, and 14 (these are the middlefour pins on each side of the op amp).

• Solder the AD745JR-16 op amps to apair of Aries 8-pin SOIC to DIPadapters.

For some strange reason, AnalogDevices made pin 3 the invertinginput on the AD745JR-16. Logically,they should have made this input pin4, so the eight pins in the middle ofthe package would exactly match thefunctions of their counterparts in the8-pin DIP package. Pin 4 is unused,so this quirk is easy to fix (Photo 34).

• Make a solder bridge between pins 3and 4 of the AD745JR-16 op amp onthe Aries header. You’d be surprisedhow difficult it is to make a solderbridge when that’s what you’re tryingto do! Now, pin 2 on the PC boardfootprint will connect to the invertinginput of the op amp.

• Install the AD745JR-16 modules inthe IC101 and IC102 footprints. Care-fully observe orientation.

HEATSINK REPLACEMENT• Remove the LT1010 buffers, IC103

and IC104. Unsolder all five leads andremove the screws that hold theheatsinks in place.

• Replace the 1″ heatsinks with the 1½″Wakefield or Aavid types recom-mended in the parts list. These arethe same type used for the pre-regula-tors in part 2. Use thermal compoundor the Adcom sili-pads, and mountthe LT1010s to the heatsinks with 6-32 hardware, without insulators. Aswith the pre-regulators, there’s noneed for insulating hardware, sincethe heatsinks do not make electricalcontact with anything.

• Replace the 22AWG jumpers J111,J112, and J115 with 18AWG jumpers.This keeps the impedance of thepower supply lines as low as possi-ble. You may need to enlarge the PCholes with a #50 drill.

Now follow the instructions for thepreamp you are building, 40dB or45.5dB. In two of the steps for each pre-amp, you will connect two resistors inseries to make the correct value. I rec-ommend standing the two resistors onend in a vise, bending the top leads atright angles, and soldering the top

leads together. Adjust the length of thetop leads and the spacing between theresistors so the series assembly willdrop into the Adcom PC footprint.

Photo 35 shows how this is done forboth Caddock and Vishay-Dale resis-tors. Refer to Fig. 9 for the 40dB, Fig. 10for the 45.5dB preamp, and Photos 32and 33 for both.

40dB PREAMP ASSEMBLY• Replace R107 (R108) with 221Ω.• Replace R109 (R110) with 1k.• Replace R111 (R112) with 15k + 2.1k

in series (RT = 17.1k).

• Replace R113 (R114) with 210k + 1kin series (RT = 211k). If you are usingCaddock resistors, the series assem-blies will straddle C115 and C116(Photo 41).

• Replace R117 (R118) with 510Ω (Cad-dock) or 511Ω (Holco or Vishay).

• Replace C111 (C112) with 2200pF.• Solder C111a (C112a)680pFto the

bottom of the PC board, in parallelwith C111 (C112).

• Solder C113a (C114a)470pFto thebottom of the PC board, in parallelwith C113 (C114).

• Replace C117 (C118) with 6800pF.


Note that C113 (C114) and C115(C116) are unchangedthe originalRoederstein KP capacitors are retained.Photo 32 shows the preamp at thisstage in the construction.

At this point, the phono preamp willoperate, but with a significant DC off-set. You should check the preamp onthe bench to verify proper operation upto this point. Apply a 1kHz sine wave to

each input at a level of10mV, and monitor oneof the tape outputbuffers. The levelshould be 1.05V, sincethe actual gain of thispreamp is 40.1dB.

Check the DC offset atthe phono preamp out-puts. Maximum outputoffset for the 40dB pre-amp will be 1.5V, andmost AD745J samplesshould be less. Don’t lis-ten to the preamp at thispoint. The DC offsetcould cause damage toother components, espe-cially your power ampand speakers!


It happens that I have had Adcom’s GFP–565 preamplifier as partof my sound system for a number of years. When Gary Galo pro-posed, some time ago, that he write a modification article for up-grading this equipment, I was pleased and yet somewhat dubiousthat the product could be improved to any significant extent. Iknew that the preamp was one of the Adcom products whose de-sign and manufacture was the responsibility of C. Victor Campos.Mr. Campos does work that is difficult to improve.

I did know that this equipmentlike any designed for the con-sumer marketwas necessarily a compromise since only hand-crafted, one-of-a-kind devices could be produced as super perfec-tionist products. Economics and competition are always issues incomponents designed for consumer markets.

Gary’s work, now published in four installments in this maga-zine, was done over several years since Gary has a demanding dayjob as well as being involved in other professional audio activities.When he was near completion of his modifications, he asked if Iwould audition the finished project. Gary asked this knowing fullwell that I would say exactly what I thought about the result, keep-ing in mind that this was an audition and that my ears are not allthey might have been in years past.

So I unpacked the two cartons containing one of his three modi-fied units, the second box containing his new external power sup-ply. I installed the new unit in the same rack with the rest of mysystem and listened carefully to three recorded samples, firstthrough the unmodified preamp, then with Gary’s modified unit inplace and then again through the unmodified unit.

The first sample is from a Telarc SACD, Lorin Maazel and theCleveland Orchestra performing Igor Stravinsky’s “The Rite ofSpring.” Second, I listened to the New Budapest Quartet playingBela Bartok’s “String Quartet No. 1” (Sz40 Op. 7.) on a HyperionDyad CD. My third sample was a Westminster Laboratory SeriesLP (W LAB 7056) with Sir Adrian Bolt conducting the Philharmon-ic Promenade Orchestra playing Benjamin Britten’s “Young Per-son’s Guide to the Orchestra.” The SACD and CD were played on aSony SACD/DVD player (DVP–NS755V) while the LP was played

on a Linn Sondek LP12, updated with a new motor from OriginLive (www.originlive.com) and a Linn Ittok LV II arm with a LINNASAK cartridge. The preamp drives two Pass Zen stereo ampseach driving one of my Thor speakers.

I am pleased to report that there are at least three notable differ-ences in the sound from the two units. First, the individual instru-ments are more clearly defined and differentiated from each other.This is most noticeable on the Stravinsky, but almost as much onthe CD. On the LP the differences were not quite as dramatic.

Second, the soundstage was quite obviously wider on all threeof the samples. The response seemed to move outside the twoThors and to fill the space in the room to a greater degree thanwith the unmodified preamp. The LP is, although very high quali-ty, a monophonic recording. The breadth and detail even on thissample was surprisingly good.

Three, the depth of the orchestral image was much greater. Onthe Stravinsky all the sound seemed to come from behind thespeakers and to even go behind the rear wall itself. My room is notideal for listening, being nearly squarewith two large door open-ings, but the speakers are carefully placed equidistant from theside walls and the back wall. The illusion of the orchestral spreadwas very firm and stable, and coupled with the increased defini-tion of the individual instruments, the effect was deeply satisfying.The quartet presence was of the four players sitting in, and slightlybehind the speakers, and quite vividly reproduced. This preamphas the ability, in my system, to help you forget that the music isbeing reproduced.

I had only one small objection to the modified result. The sepa-rate power supply is housed in a stock aluminum box which has avery slight vibration at what sounds like 120Hz. A slight pressureon the top of the box quiets the noise very effectively. A remedyshould be easy.

I believe the modifications Gary has made to his units are a veryworthwhile undertaking, even considering the amount of work in-volved. His modified Adcom GFP 565 is probably the best sound-ing preamp I have ever had the pleasure of auditioning.E.T.D.

LISTENING TO GALO’S MODIFIED ADCOM GFP–565

PHOTO 36: The Old Colony DG13R circuitboard modified for use as the DC servo board.Five traces are cut, and several new holes aredrilled to accommodate the servo circuit.

PHOTO 37: Bottom and top views of the DC servo board.R151, R152, C157, and C158 are soldered to the bottom ofthe board. Only one board is needed for both channels.

45.5DB PREAMP ASSEMBLY• Replace R107 (R108) with 121Ω.• Replace R109 (R110) with 499Ω.• Replace R111 (R112) with 17.4k +

200Ω in series (RT = 17.6k).• Replace R113 (R114) with 210k + 1k

in series (RT = 211k). If you are usingCaddock resistors, the series assem-blies will straddle C115 and C116(Photo 41).

• Replace R117 (R118) with 332Ω.• Replace C113 (C114) with 680pF.• Solder C113a (C114a)220pFto the

bottom of the PC board in parallel

with C113 (C114).

Note that C111 (C112), C115 (C116),and C117 (C118) are unchangedtheoriginal Roederstein KP capacitors areretained. Photo 32 shows the preamp atthis stage in the construction. At thispoint, the phono preamp will operate,but with a significant DC offset. Youshould check the preamp on the benchto verify proper operation up to thispoint. Apply a 1kHz sine wave to eachinput at a level of 5mV, and monitorone of the tape output buffers.

The level at the output of the phonopreamp should be just under 0.96V.Check the DC offset at the phono pre-amp outputs. Maximum output offsetfor the 45.5dB preamp will be 3V, andmost AD745J samples should be less.Don’t listen to the preamp at this point.The DC offset could cause damage toother components, especially yourpower amp and speakers!

DC SERVO CONSTRUCTIONThe DC servo is the same for both pre-amps. I built the servo on one of Ed


PHOTO 38: Bottom view of the DC servo board with input, output,and power supply leads attached.

PHOTO 39: Side view of the completed phono preamp with theservo board installed. The servo board is mounted to the preamp’smetal side rail with angle brackets.


If you can afford an Audio Precision System 1or System 2, its built-in algorithms makeRIAA measurement relatively easy. For therest of us, measuring RIAA accuracy is atricky and tedious process, requiring theright equipment and a lot of patience. I havedeveloped a procedure using conventionalequipment that works very well.

For many years I have used the Jung-Lipshitz inverse RIAA network, which is apassive device I built from the Old Colonykit, with 1%-tolerance parts (no longer avail-able)3. But, matching your generator sourceimpedance to this network can be frustrat-ing, and a source of error. Jung and Lipshitzoffered two versions of the network, withcomponent values trimmed to accommodatesource impedances of 0Ω or 300Ω.

The problem is that most generators haveoutput impedances in the 500 to 600W range.I decided to actively buffer my Jung/Lipshitznetwork. I ran some computer simulations tocheck the accuracy of the buffered deviceagainst Walt’s mathematically ideal RIAA de-emphasis network, and found that the bestaccuracy was with the 0Ω source impedancenetwork driven directly from IC1’s output(Fig. 16). My simulations showed an excellentresponse across most of the spectrum, withan error of only −0.024dB at 20kHz (Fig. 17).

The op amps for IC1 and IC2 need to be high-current de-vices capable of driving a 600Ω load, which is the terminatingimpedance of the network. The op amp should also be a low-offset, FET-input device, to allow DC coupling. A noisy op ampcan cause meter readings to wander, particularly at lower fre-quencies. I had this problem with Analog Devices AD845, so Ichanged the op amps to TI/Burr-Brown OPA627BP devices,which can deliver 45mA of output current, with an input volt-age noise of 4.5nV√Hz at 10kHz.

The difficulty in measuring RIAA response is the need to re-solve differences in the hundredths of a decibel. Most signalgenerators do not maintain exactly the same output at all fre-quencies, and most meters have variations, as well. Accurate,high-resolution dB meters are rare, and the popular LoftechTS-1 and TS-2 have only 0.1dB resolution, making them useless forRIAA measurements. The best choice is an AC DMM with 20kHzbandwidth and 1mV resolution. I used the generator in my SoundTechnology 1700B and a Tenma (MCM Electronics) 72-410A bench-type, true-RMS DMM.

I first tested the accuracy of the generator and DMM as a system,after warming up the test equipment for two hours. I set the genera-tor to 1V output at 1kHz, and fine-tuned the output so the DMM readexactly 1.000V. I then ran a decade frequency response test from20Hz to 20kHz, noting the exact voltage reading at every frequency.Over the course of two days, I re-checked the errors several times tosee whether the measurements were repeatable. They were.

I plugged these error figures into a spreadsheet (MicrosoftExcel), which allowed me to automatically correct for the genera-tor/meter error. If the generator and meter read 1.007V at 20kHz,as an example, my correction column has −0.007V as the correc-tion needed.

To measure the preamps, I inserted my active Jung/Lipshitz in-verse RIAA network between the generator and the phono inputon the preamp, set the generator output to 1V, and connected thepreamp’s main output to the DMM (remember that I treated thephono preamp plus line-stage loading as a system). The inverse

network’s 40dB insertion loss cuts the level down to 10mV at thepreamp’s phono input.

The preamp’s volume control is carefully adjusted to make theDMM read 1.000V at 1kHz. Then I ran a complete decade frequen-cy response check from 20Hz to 20kHz (in 1kHz steps between10kHz and 20kHz), writing the results down in the “measured” col-umn in the spreadsheet. I put a formula into the spreadsheet totake preamp measurement and necessary generator/meter correc-tion to give a “corrected” response in the next column.

The spreadsheet converted the voltage measurements to dB,using the formula:

dB = 20 log (E1/E2)

where E2 is the 1.000V reference at 1kHz and E1 is the measure-ment at the other frequencies. This gave the correct ±dB indicationin the “response in dB” column. I also entered the errors of thebuffered inverse RIAA network above 1kHz, using data from mycomputer simulation. I did this for both channels, and then usedExcel to make a graph with both the left and right curves (Figs. 14and 15). This procedure is extremely painstaking, but it seems tobe accurate and repeatableGG.

MEASURING RIAA ACCURACY

Jung/Lipshitz RIAAEmphasis Network

W. Jung: RIAA Demphasis NetworkVcVs1 Scaling = 9.89805 * 10^[(1kHz gain in dB)/20]

All Parts1% Tolerance

++

OPA627BPIC2

++

OPA627BPIC1

V2-15V

V3+15V

Ct100pF

V4-15V

V5+15V

C11nF

C55pF

C41nF

C33.6nF

1kHz

V1-1/1V

+

-

VcIs213.3333333e-6

+

-

VcIs10.34940601e-6

C21nF

+

-

+

-

VcVs11586.86

R1149.9

R71Meg

R22.862Meg

R1318k

R10604

R912Meg

R875k

R6845k

R538.3k

R375k R4

47k

FIGURE 16: Simulation circuit for testing the buffered Jung/Lipshitz inverse RIAA network.The network is checked against a mathematically ideal RIAA de-emphasis model.

A-2313-16


100.00mdB

50.00mdB

0.000mdB

-50.00mdB

-100.0mdB

-150.0mdB

-200.0mdB

-250.0mdB

-300.0mdB

A: vcvs1_3

Measurement Cursors1 vcvs1_3 X: 557.23 Y: -7.8240m2 vcvs1_3 X: 19.869k Y: -31.633mCursor 2 - Cursor 1 X: 19.312k Y: -23.809m

FIGURE 17: Error of the buffered inverse RIAA network, com-pared to the mathematically ideal de-emphasis model. The net-work is ruler-flat to 1kHz, and down only 0.024dB at 20kHz.

A-2313-17

Dell’s venerable DG13R electroniccrossover boards, sold by Old Colony. Istill find this op-amp PC board to be ex-tremely versatile, and I have adapted itfor a variety of projects over the years.

You need only one board for bothchannels. You can also use a small perf-board, if you wish. You can easily adaptthe DG13R board for this circuit by cut-ting a few traces, adding a couple ofjumpers, and drilling a few new holes(Photos 36, 37, and 38).

• Cut the five traces on the DG13Rboard shown in Photo 36.

• Photo 36 also shows the locations ofextra holes that you must drill in thePC board. Use a #55 drill.

• Assemble the servo components onthe board, using Photos 37 and 38 asa guide.

• R151 and R152 are soldered to thebottom side of the PC board. All otherservo parts are mounted on the top ofthe board.

• C155 and C156the 100µF electrolyt-ic supply bypass capacitors shouldbe mounted on the top of the board.

• C157 and C158the 1µF film bypasscaps—are soldered to the bottom of theboard, in parallel with C155 and C156.

• Solder 2″ lengths of 18AWG hookupwire for the input and output connec-tions for each channel. I used blackwire for the inputs and red for theoutputs (Photo 38).

• Solder three 18AWG hookup wiresfor the positive and negative supplyconnections, and ground. Make thesewires long enough to reach the bot-tom of the PC board, where you willsolder them to the main preamp sup-ply bus. I used red wire for positive,white for negative, and black forground (Photo 38).

Check the assembly of the servoboards very carefully to make sure thateach channel matches the schematicsin Fig. 9 or 10. Clean the PC board withCaiCleen TRP DG7S-6 Cleaner. Clean-ing is extremely important, becauseresidual solder flux can cause leakagesin these high impedance circuits.

SERVO BOARD MOUNTINGThe DC servo input connections aretaken from holes left vacant by the re-moval of R115 and R116. You must

drill two new holes for the output con-nections:

• Drill a small hole with a #50 drillthrough the PC board between the va-cant R115 holes. Make sure that thishole lands in the middle of the PCtrace that goes between the R115holes on the bottom of the board.Scrape enough lacquer off the PCtrace to ensure a good connection.

• Drill a small hole with a #50 drillthrough the PC board between the va-cant R116 holes. Make sure that thishole lands in the middle of the PC

trace that goes between the R116holes on the bottom of the board.Scrape enough lacquer off the PCtrace to ensure a good connection.

• Enlarge the R115 and R116 holesclosest to C112 and C113 with a #50drill.

You can mount the DC servo boardon the preamp’s metal side rail withtwo small angle brackets, 1/8-nylonspacers and 4-40 hardware (Photos39, 40, and 41). The board will sit di-rectly above the old C107 to C110footprints on the main PC board.

• Mount two angle brackets to the end


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of the servo board with the powersupply connections. Use nylon spac-ers, 4-40 machine screws, lock wash-ers, and nuts. The Mouser bracketsrecommended in the parts list haveone hole tapped for a 4-40 machinescrew. I used the tapped hole tomount the board/bracket assembly tothe preamp’s metal side rail.

You’ll need to drill two holes in thepreamp’s side rail to mount theboard/bracket assembly.

• Position the board as shown in Photo39, and mark the locations of the twomounting holes.

• Drill the two holes with a ¹⁄₈″ drill. Isuggest removing the metal side railbefore drilling, and re-mounting itafter. The side rail is held in placewith six screws, and is easy to remove.

• Put the metal side rail back in place,but don’t mount the servo board as-sembly just yet.

Trim the servo input and outputleads when you connect them to themain PC board, to keep them as shortas possible (Photos 40 and 41).

• Solder the left servo input lead to thehole previously occupied by the R115resistor lead, closest to C111.

• Solder the left servo output lead tothe newly drilled hole next to theinput lead.

• Solder the right servo input lead tothe hole previously occupied by theR116 resistor lead, closest to C112.

• Solder the right servo output lead tothe newly drilled hole next to theinput lead.

• Route the three power-supply wiresto the bottom of the main PC board,between the main PC board and theside rail.

• Fasten the servo board assembly tothe side rail with two 4-40 machinescrews, using the tapped holes in theangle brackets. There should be plen-ty of clearance between the main PCboard and the components on thebottom of the servo board.

• Solder the positive and negative sup-ply wires, and the ground wire, to themain supply buses on the bottom ofthe PC board (Photo 33).

The phono preamp and DC servomodifications are now complete. Care-fully re-check all of the assembly tomake sure that your preampinclud-


PARTS LISTNOTE: ALL RESISTORS ARE BUILDER’S CHOICE:Vishay–Dale CMF Type RN60 (Welborne Labs, Mouser 71–RN60D–Value)

Holco H4 (older non–ferrous type, if available, Welborne Labs, Michael Percy Audio, Parts Connexion)

Caddock MK132 (Welborne Labs, Michael Percy Audio, Parts Connexion)

Vishay S–102 (Michael Percy Audio)

DC servo (same for both preamps):

(1) DG13R circuit board, Old Colony PCBC–4

(2) Analog Devices OP97EP op amp, Newark 66F5763 or Analog.com

(4) 0.22µF (220nF) 160V Wima MKP–10 capacitors, Welborne Labs WM214 (C151, C152, C153, C154)

(4) 499k ½W resistors (R151, R152, R153, R154; use Vishay–Dale CMF type RN60 or Holco H4)

(2) 1.5M ½W resistors (R156, R157; use Vishay–Dale CMF type RN60 or Holco H4)

(2) 100µF, 25V DC Nichicon KZ, Michael Percy Audio (C155, C156)

(2) 1.0µF, 50V DC Mallory 168–series, Newark 89F1692 (C157, C158)

MISC.Angle brackets, Mouser 534–616

¹⁄₈″ nylon spacers, Digi–Key 875K–ND

4–40 hardware

18 AWG hookup wire: Welborne Labs TWR, TWB and TWW (Welborne Labs);

40dB phono preamp:

(2) Wakefield 634–15ABP 1¹⁄₂″ heatsink, Newark 91F3674—or—Aavid 581102B00000, Digi–Key HS303–ND (for LT1010 buffers)

(2) Analog Devices AD745JN op amp, 8–pin DIP, Rochester Electronics—or—Analog Devices AD745JR–16 op amp, 16–pin SOIC, Analog.com (IC101, IC102)

(2) Aries 8–pin SOIC/DIP adapters, Digi–Key A724–ND (adapters needed only for the AD745JR–16)

(2) 47.5k resistor (R103, R104)

(2) 33Ω ½W resistor (R119, R120; use Vishay–Dale CMF type RN60 or Holco H4)

(2) 100Ω ½W resistor (R121, R122)

(2) 221Ω ½W resistor (R107, R108)

(4) 1k ½W resistor (R109, R110, R113, R114)

(2) 15k ½W resistor (R111, R112)

(2) 2.1k ½W resistor (R111, R112)

(2) 210k ½W resistor (R113, R114)

(2) 510Ω ½W resistor (R117, R118; 510Ω is the Caddock value carried by Welborne; use 511Ω for Holco or Vishay–Dale)

(2) 2200pF 100V 2.5% Wima FKP–2, Welborne Labs WM9 (C111, C112)

(2) 680pF 100V 2.5% Wima FKP–2, Welborne Labs WM6 (C111a, C112a)



45.5dB phono preamp:

(2) Wakefield 634–15ABP 1¹⁄₂″ heatsink, Newark 91F3674—or—

Aavid 581102B00000, Digi–Key HS303–ND (for LT1010 buffers)

(2) Analog Devices AD745JN op amp, 8–pin DIP, Rochester Electronics—or—Analog Devices AD745JR–16 op amp, 16–pin SOIC, Analog.com (IC101, IC102)

(2) Aries 8–pin SOIC/DIP adapters, Digi–Key A724–ND (adapters needed only for the AD745JR–16)

(2) 47.5k resistor (R103, R104)

(2) 33Ω ½W resistor (R119, R120; use Vishay–Dale CMF type RN60 or Holco H4)

(2) 100Ω ½W resistor (R121, R122)

(2) 121Ω ½W resistor (R107, R108)

(2) 499Ω ½W resistor (R109, R110)

(2) 17.4k ½W resistor (R111, R112)

(2) 200Ω ½W resistor (R111, R112)

(2) 210k ½W resistor (R113, R114)

(2) 1k ½W resistor (R113, R114)

(2) 332Ω ½W resistor (R117, R118)



ing the DC servo and its connections tothe main PC boardmatches theschematic diagrams. Clean the mainPC board with CaiCleen TRP DG7S-6Cleaner.

TESTINGNow it’s time for some tests. Move thelistening selector to Video/Aux (just toget it out of the way, for now). Put short-ing plugs in both of the phono inputsand check the DC offsets with a digitalmultimeter (DMM) at the outputs ofeach channel. The easiest place to readthe left channel is at jumper J114; mea-sure the right channel at the junction ofR118 and C118. The DC offsets in thethree preamps I built are very close to0V. The noise from the phono preampswill make a DMM wander a few tenthsof a mV either side of zero on the200mV scale (or whatever your meter’smost sensitive DC scale happens to be).

The 45dB preamp makes my DMMwander a little more than a mV eitherside of zero, since the noise level ishigher in the preamp. But, you can alsolook at the offset on a scope set to 5mVor 1mV per division. With your probegrounded, carefully set the trace in thecenter of the screen, and then look atthe offset with your probe.

On my preamps, I see random noiseabove and below the zero line, but noreal shift in the DC level. The offset read-ings should be close to the same regard-less of the source impedance. In otherwords, there should be little difference

in the readings with shorting plugs orwith the phono inputs wide open (whenyou change the source Z, the servo doestake a few seconds to settle).

After you’ve put the covers back onthe preamp, you can still check thephono DC offset at the tape outputs. Putthe recording selector in the CD posi-tion. Check the DC offsets at either ofthe left and right tape outputs, and notethe readings. If you used OPA2604 opamps for the tape output buffers, the out-put offsets will be no more than 5mV.

Now move the recording selector tothe phono position to read the com-bined tape buffer and phono preampoffset. The offset at the tape outputs willwander above and below the readingsyou obtained with the recording selec-tor in the CD position, but about thesame amount they did when youchecked the offset directly from thephono preamp outputs. If your testsmatch these, the DC servo is operatingproperly. I highly recommend runningthe preamp on the bench for 24 hoursand re-checking the DC offset.

If you have a distortion analyzer, youcan compare the THD and IMD of yourpreamp to the measurements in Table1, which shows the measurements Imade on the preamp I modified for Vic-tor Campos, which has 40dB of gain. Iused a Jung/Lipshitz passive inverseRIAA network, and adjusted the genera-tor output at 1kHz for 2V at the tapeoutputs. My noise measurements weremade relative to 2V at the tape outputs.To measure the residual noise, I re-moved the signal generator from thephono input and inserted 100Ω resistor

plugs in the phono inputs, simulating alow-impedance cartridge.

My measurements show noise fromthe 40dB preamp to be 94.5dB below2V out, unweighted. Adcom specifiesthe noise for the original preamp at95dB below 2V, but A-weighted. Themodified preamp has lower noise thanthe original.

I discuss my measurement proce-dure for RIAA accuracy in the sidebarthat accompanies this article. The re-sults are shown in Figs. 14 and 15. Fig-ure 14 is the response of the 40dB pre-amp. The 20Hz to 20kHz RIAA accuracyis ±0.036dB for the left channel and±0.04dB for the right. Figure 15 is theresponse of the 45.5dB preamp. The20Hz to 20kHz RIAA accuracy is±0.0825dB for the left channel and±0.0655dB for the right.

Both preamps are well within the tar-get of ±0.1dB, and every bit as good asthe Adcom originals as measured bythe manufacturer with an Audio Preci-sion System 1 (the 40dB measurementsare actually an order of magnitude bet-ter than the Adcom originals). With theconclusion of this preamp modificationproject, there’s nothing left for you todo but listen and enjoy the music.


REFERENCES1. Lipshitz, Stanley P. “On RIAA Equalization Net-works,” Journal of the Audio Engineering Society, V.27, No. 6, June 1979, pp. 458-481.

2. Although I have found CircuitMaker 2000 to be agood program, their technical support leaves a lot to bedesired. There are a number of known issues with theprogram that the manufacturerAltium, Ltd.seemsto have no interest in fixing (www.circuitmaker.comand www.altium.com), but I have learned how to workaround them. The program does offer a great deal forthe money, including schematic capture, mixed-signalsimulation, and PC layout.

3. Lipshitz, Stanley P., and Walt Jung. “A High Accura-cy Inverse RIAA Network,” Audio Amateur, 1/1980.

VENDORS:Old Colony Sound LaboratoryPO Box 876Peterborough, NH 03458-08761-888-924-9465 1-603-924-9464 1-603-924-9467 (FAX)[email protected]

Rochester Electronics, Inc.10 Malcolm Hoyt DriveNewburyport, MA 01950978-462-9332 978-462-9512 (FAX)[email protected]

(Remaining vendors are listed in Part 1)

PHOTO 40: Close–up of the phono preampshowing the input and output connectionsto the servo board. This preamp was builtwith a combination of Holco andVishay–Dale resistors.

PHOTO 41: Close–up of a phono preampbuilt with Caddock MK132 resistors. Theseries resistors that make up R113 andR114 straddle C115 and C116.

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