Post on 15-Jan-2017
HF TRANSCEIVER
Prof. Yosef PINHASI
The transceiver presented in this article is designed to operate in the radio amateur bands of the HF frequencies (3-30MHz). It was constructed on four printed circuit boards:
• Receiver and audio amplifier
• Intermediate frequency (IF) modulator and product detector
• Up-converter mixer and radio frequency (RF) power amplifier
• Transmit / Receive (T-R) relay and RF low pass filter.
A block diagram of the transceiver is illustrated in Figure 1. In order to avoid mutual electromagnetic interferences, the receiver and IF sections are separated from the RF power stage. This requires transferring three signals between the two units; IF double-side band (DSB) modulated signal, local oscillator and the RF antenna signal. Much effort has been directed to keep the design simple and compact by utilizing integrated circuits and direct couplings. Each of the four single-sided PCBs has its own power supply, including a voltage regulation circuitry. In its present version, the transceiver is operating in the 20m amateur band, covering 14.000-14.350MHz. The receiver can detect AM, FM and SSB signals, while the transmitter operates in a DSB
mode.
RF 455KHz
VFO
Quadrature
detector
AF
AM
FM
S A 6 0 5
3 14
7
9
1
LM380
Buffer
2N918
RECEIVER
LNA
MPSH10
AUDIO OUT
VFO
Balanced mixer
Driver IF
455KHz
TRANSMITTER RF
SA602
PA
2N3553
2N2222
Buffer
DSB
Balanced modulator
AF
LM741
MC1496 TONE
1KHz
2N3904
BC149
455KHz IF
BALANCED MODULATOR & PRODUCT DETECTOR
MICROPHONE
AUXILARY
MIC.
TONE
BFXO
2N 918
2N2222
Buffer
455KHz IF CW/SSB
Product detector
455KHz
2N4416 BFXO BFO
7404
FREQUENCY
COUNTER
2N3866 MRFMRFMRFMRF150150150150
Figure 1: Block diagram of the HF transceiver.
I. THE RECEIVER
Figure 2 is the electronic scheme of the receiving module. The front-end of the receiver consisted of a 4.7µH inductor in series with a 27pF capacitor, constituting a resonant circuit at 14.128MHz. The two diodes at the input protect from excessive signals by clipping spikes and large amplitudes that may damage the receiver front-end. The series resonant filter it is followed by an impedance matching network
transferring the aerial 50Ω impedance into 4.5KΩ input impedance of the SA605 RF stage. The matching network is shown in Figure 3.a and its transmission characteristics of the matching network are shown in Figure 3.b.
1N4148
0.1u
50p
0.1u
0.1u
Au
dio
(to
au
dio
am
plif
ier)
SA605
1 2 3 4 5 6 7 8 910
20
19
18
17
16
15
14
13
12
11
1N4148
1N4148
BF
XO
(from
mo
du
lato
r)
2N2222
4.7K 1K
47K
10n
40n
270
270
1N4148
CW / SSB
1N4148
470p
22K
470p
5.1K
5.1K
10n
1K
10n
+12V
4.7u
470
50p
VFO (to mixer and power amplif ier)
BNC
1
2
0.1u
1n 1n
0.1u
2.7K
2N918
2K
680K
10n
2N2222A
20K
100K
51010n
10n
5.1K
10n
24 t
urn
s T
-50-6
2.3
uH
FM
AM
AMAMAM
6.2V+
100u
470pF
455K
Hz b
lack I
F
12 t
urn
s T
-50-6
0.5
77uH
56pF
0.1u
BB109RFC1mH
10p
27p
0.1u
RF
in (
from
T/R
rela
y)
BNC1
2
680
1N4148
100K
0.47u
1n
220K
100K
15n 150p
100K
1K
100K
100K
455KHz
2
31
120pF
AM / FM
+12V
455KHz
2
31
50pF
0.1u
0.1u
10V
S
S
455KHz black IF
2
1
3 4
6
0.1u
+
47u
Figure 2: The receiver and product detector.
24 t
urn
s T
-50-6
2.3
uH
470pF
56pF
Input
1
2
4.5K
50 Ohm
(a) (b)
Figure 3: Front-end impedance matching network: a) scheme, b) power transmission.
The main receiving chain is based on the Philips SA605 mixer and IF system [1]. This integrated circuit (previously manufactured by Signetics with the number
NE605) is a super-heterodyne receiver composing of an internal balanced mixer, local oscillator and intermediate frequency amplifiers. The 6.2V regulated supply voltage required at leg 7 is achieved by employing a zener diode. The local oscillator (L.O.) of the SA605 is based on a varactor-tuned variable frequency oscillator (VFO). The L.O. frequency should be 455KHz below the receiving frequency, i.e. 13.545-13.895MHz. In this Colpitts configuration, the frequency is determined by the coil L3, the varactor CV and the two parallel capacitors C3a and C3b, as shown in Figure 4.a. The oscillation frequency of the L.O. is following the expression:
( )( )
+⋅
++
=
21
21332
1
CC
CCCVCL
Vf
V
LO
π
While using the BB109, I found out that the coil inductance should be L3=0.577µH (12 turns on a T-50-6 iron powder toroid yellow core). The capacitor is approximately C3=150pF made of a C3a=120pF capacitor in parallel with a C3b=50pF trimmer (see Figure 4.a). In that case, the receiving frequency as a function of the voltage introduced to the varactor is shown in Figure 4.b. Note that besides the main 14.000-14.350MHz band (455KHz above the L.O. frequency), also image frequencies of 13.09-13.440MHz (455KHz below the L.O.) are expected to be detected as a result of a super-heterodyne configuration.
C1=50p
C2=50p
1n 1n
12 t
urn
s T
-50
-6
L3=
0.5
77u
H
C3a C3b
4
3 Cv
BB109
Vtune
+
-
(a) (b)
`Figure 4: The VFO: a) Resonant circuit, b) Receiving frequency as a function of the voltage in the 20m bands. The image frequencies are also shown.
The continuous local oscillator sine wave appearing in leg 3 is also transferred to the up-conversion mixer in the transmitting unit of the transceiver, via a buffering 2N918
transistor in the receiver module followed by 2N2222A transistor (located in the transmitting module). Two standard 455KHz ceramic filters are used in the IF stage. The SA605 is originally designed as an FM receiver; it includes a limiter and an FM quadrature detector, as well as an RSSI (received signal strength indicator). When an FM signal is received, the demodulated information is obtained at the unmuted audio output (leg 9). A black 455KHz standard IF transformer is used in the quadrature detection system. Appropriate design of the RSSI filter, enables also detection of AM signals. In that case the demodulated audio is obtained at the RSSI output (leg 7). In order to detect CW or SSB transmissions, an external product detector is added.
Here, a switching two-diode detector was chosen, driven by a 2N2222 bipolar transistor and an additional 455KHz black IF transformer. The detector, which in this construction is part of the IF PCB, is connected to leg 14 (the input of the SA505 limiter), where the IF signal is obtained. The 455KHz beat frequency is generated by a crystal oscillator (BFXO) in the IF board. The audio amplifier is shown in Figure 5, including the 12V regulated power supply of the whole receiver unit. The audio amplifier is composed of the LM380 producing
about 2W of RMS power over a 8Ω loudspeaker.
+
470u+
- LM380
2
36
874 5
100K+
47u
+1u100K
100K
7812
IN3
OUT1
+
10u
SPEAKER
+-
~ ~
Q12N3906
+12V
4.7K
10K
1n
0.1u+
1000u
0.1u
0.1u
4.7K
MUTE123
Audio (f rom receiver)
PHONES
12345
Figure 5: Audio amplifier and receiver 12V power supply.
II. THE IF BALANCED MODULATOR
The modulator section is based on the Motorola MC1496 balanced modulator integrated circuit [2]. Audio signals from microphone, external auxiliary line or internal tone generator are combined together by an operational amplifier TL071 (Equivalent to the 741). The microphone signal is fed to a single transistor pre-amplifier, enabling utilization of a standard 600Ω dynamic microphone or an electrostatic. The transistor BC149 was chosen due to its low noise performance but any other small-signal transistor will do well. The level of the microphone can be adjusted by an external potentiometer, changing the modulation level. A tone of 1,000Hz is generated by a single 2N3904 (or equivalent) transistor phase-shift oscillator, which can be switched on for transmitter testings. An internal on-board trimmer is used for setting tone modulation level. The auxiliary input impedance is 47KΩ, similar to that of standard audio inputs. The voltage gain of the TL071 audio amplifier is 20, producing 300-500mVpeak to the signal input of the balanced
modulator. The modulator generates a double-side band suppressed-carrier signal centered at an intermediate, sub-carrier frequency of 455KHz. The sub-carrier is produced by the beat frequency crystal oscillator (BFXO) based on the JFET 2N4416. The same signal is used also for the product detection in the receiver. The oscillator, is buffered by a two stage amplifier, consisting of the common emitter 2N918 followed by a common collector 2N2222. This is required in order to feed the low impedance carrier input of the balanced modulator with 60-100mVpeak of 455KHz continuous wave. A trimmer is adjusted for best carrier null the output. In order to enable CW or amplitude modulation transmission, violation of the carrier balance is created, by connecting a 1KΩ resistor from leg 4 to the ground.
The balanced modulator, 455KHz oscillator, audio preamplifier and tone generator are all constructed on the same PCB including their 12V regulated power supply.
820
7812
IN3
OUT1
1.2K
RFC
1mH
0.1u
1K
Tone
+
10u0.1u
MIC
RO
PH
ON
E
1
23
+
10u0.1u
MC1496
1 2 3 4 5 6 7
11
12
13
14
8910
10K
47K
-
+TL0713
26
7 14 5
47K
5.1K
1M
5.1K
+
10u
+
1u +
1u
1K +10u
2N3904
50K
47
+
1u
10K100K
10K
10n
10K
10K
2.7K
10n
10K
10n
10K
2N2222A
2N918
240
10n
12K
820
47K
15n3.6K
180
2N4416
100K1N41481n
1n
455
KH
z
1n6.8V
+
100u
50n
50K
180
BC149100K
+
1u
10K
56n
10K
+
10u
1K
CW / AM
0.1u
AU
XIL
IAR
Y 123
10K 10K
+-
~ ~
1.5M
1n
150p
0.1u+
10m
455K
Hz
DS
B (
to t
rans
mit
ter)
RCA JACK
1
2
100 100
1K
47K
2.7K
Figure 6: Intermediate frequency balanced modulator.
III. THE UP-CONVERSION MIXER AND POWER AMPLIFIER
The unique structure of the transmitter unit shown in Figure 7, is aimed at simplification of the coupling between the mixer, driver and final amplifier. These three stages are constructed on a single PCB, installed in a separated enclosure, to minimize RF interferences to the sensitive receiver. The up-conversion mixer is the well known SA602 double-balanced mixer and oscillator [3]. A 6.2V zener diode is employed to regulate the voltage supplied to the mixer. The double-side band, suppressed-carrier signal from the MC1496 balanced modulator (in Figure 6), is fed to the oscillator input (leg 6) of the SA602 mixer. A 455KHz ceramic band pass filter is used to reduce inter-modulation products of the sub-carrier before the up-conversion process. As mentioned before, the internal VFO of the SA605 receiver (shown in Figure 2) serves also as the local oscillator of the transmitter. The continuous sinusoidal wave of the VFO, shifted 455KHz from the
transmission carrier frequency is fed to the input of the mixer (leg 1). Two RF suppressed carrier modulated signals are generated at the output ports of the balanced mixer, legs 4 and 5, with a 180˚ phase difference between each other. This enables a direct coupling to the subsequent push-pull driver. The driver is based on high frequency bipolar junction transistors, the 2N3866 followed by the 2N3553. This stage is biased to operate in a class A mode, drawing a quiescent current of 80-100mA from a 12V regulated power supply. The total power dissipation at this stage is approximately 1W, requiring installation of heat sinks on the 2N3553 transistors. The switch, operating the mixer and driver, also serves as the PTT of the transmitter. The driver is coupled to the power amplifier section via a 3:1 transformer, reducing the impedance by a factor of 9 as explain in [4]. The primary
supplies the voltage to the collectors of the 2N3553, while the secondary applies the bias to the gates of the MRF150 field effects transistors of the final amplifier. The transformer is made of a 22AWG enameled wires wound through a BN-43-202 ferrite core, 3 bifilar windings for the primary and a single winding for the secondary. Two MRF150 field effects transistors (FETs) serve in the final push-pull power stage. The MRF150 transistor is an N-channel, enhancement-mode FET, designed primarily for delivering 150W, with 45% efficiency at 50V. It is often used in broad-band linear amplifiers operating in the HF band [5-8]. In the present design both gates are biased from the same regulated 5V source. The positive bias is adjusted by a 10KΩ trimmer for a quiescent current draw of 200mA from the 50V power supply. In order to avoid oscillations, two 1Ω are used, isolating the paralleling inductance, from the gates as noted in [6-7]. The power transistors should be mounted on a proper heat
sink for efficient removal of the dissipated heat.
MRF150
MRF150
455KHz
2
31
0.1u
10K
10K
100
100
15n
1.2K
Red
15n
0.1u100
SA602
1 2 3 45678
VF
O (
fro
m r
eceiv
er)
BNC1
2
100p
10
2N3553
2N3866
220
6.8K
1.2K
10
1
7805
IN3
OUT1
1
0.1u
10n1.8K
10K
Green
82 +-
~ ~
1.8K
470
Driver
10n
1N4005
Yellow
RF
ou
t (t
o T
/R r
ela
y)
1n
0.1u+
10m , 63V
0.1u
A 5A
+
10u
0.1u
2N3553
2N3866
220, 10W
0.1u
10 b
ifila
r tu
rns F
T-5
0-4
3A
1
42
3
7812
IN3
OUT1
10n
+
10uPower Amplif ier
1M
RFC390u
Bias
BN-43-202
3 : 1
1 4
5
3 6
2
T / R Control (to T/R relay)
220
470
6.8K6.2V
1.2K
10n
+100u
0.1u
0.1u
500mA
5A
22V , 5W
455
KH
z D
SB
(fr
om
modu
lato
r
RCA JACK1
2
BN-43-7051
1 : 31 3
2 4
(a)
(b)
Figure 7: The up-converter and power amplifier stage a) schematics, b) photo.
IV. T/R relay and Filter
2N3019
RF in (to receiv er)BNC
1
2 T/ R RELAY DPDT
34
5
68
712
10
1N914
470
7812
IN3
OUT1
0.1u+
10u
ANTENNA
SO2391
2
RF out (f rom transmitter)
0.1u
220p 220p
T/ R
con
tro
l (fr
om
tra
ns
mitt
er)
T / R
indic
ato
r
PHONEJACK123
4N26
12
54
5.1K
4N26
12
54
8turns T-50-2
320n
2N3019
8turns T-50-2
320n
12turns T-68-6
668n
1n
0.1u+
1000u, 63V
22V , 5W
+-
~ ~
1K
Filter calculation from http://www.wa4dsy.net/filter/hp_lp_filter.html
V. References
1. A. K. Wong: "Reviewing key areas when designing with the SA605", Philips Semiconductors application note AN1994 (November 2007)
2. R. Hejhall: "MC1496 Balanced Modulator", Motorola Semiconductors application note AN531/D (January 2002)
3. "High sensitivity applications of low-power RF/IF integrated circuits", Philips Semiconductors application note AN1993 (August 2007)
4. H. Granberg: "Broadband transformers and power combining techniques for RF", Motorola Semiconductors application note AN749/D (January 2002)
5. H. Granberg: "MOSFET RF power in the kW level: An update", QST Part 1 (December 1982) and Part 2 (January 1983)
6. H. Granberg: "Get 600 Watts RF from four power FETs", Motorola
Semiconductors application note EB104 (1983) 7. H. Granberg: "Get 600 Watts RF from four power FETs", Motorola
Semiconductors application note EB104/D (1993) 8. T. Sowden: "Hombrew solid-state 600WHF amplifier", QST (June 2006)